Apparatus for transmitting broadcast signals, apparatus for receiving broadcast signals, method for transmitting broadcast signals and method for receiving broadcast signals

ABSTRACT

The present invention provides a method of transmitting broadcast signals. The method includes, formatting input streams into Data Pipe, DP, data; Low-Density Parity-Check, LDPC, encoding the DP data according to a code rate; bit interleaving the LDPC encoded DP data; mapping the bit interleaved DP data onto constellations according to one of QAM (Quadrature Amplitude Modulation), NUQ (Non-Uniform QAM) or NUC (Non-Uniform Constellation); Multi-Input Multi-Output, MIMO, encoding the mapped DP data by using a MIMO encoding matrix having a MIMO encoding parameter; building at least one signal frame by mapping the MIMO encoded DP data; and modulating data in the built signal frame by an Orthogonal Frequency Division Multiplexing, OFDM, method and transmitting the broadcast signals having the modulated data.

This application is a continuation of application Ser. No. 14/256,817,filed Apr. 18, 2014, and claims the benefit of U.S. Provisional PatentApplication No. 61/814,323 filed on Apr. 21, 2013, 61/841,412 filed onJun. 30, 2013, 61/883,957 filed on Sep. 27, 2013 and 61/968,367 filed onMar. 21, 2014, which is hereby incorporated by reference as if fully setforth herein.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to an apparatus for transmitting broadcastsignals, an apparatus for receiving broadcast signals and methods fortransmitting and receiving broadcast signals.

2. Discussion of the Related Art

As analog broadcast signal transmission comes to an end, varioustechnologies for transmitting/receiving digital broadcast signals arebeing developed. A digital broadcast signal may include a larger amountof video/audio data than an analog broadcast signal and further includevarious types of additional data in addition to the video/audio data.

That is, a digital broadcast system can provide HD (high definition)images, multi-channel audio and various additional services. However,data transmission efficiency for transmission of large amounts of data,robustness of transmission/reception networks and network flexibility inconsideration of mobile reception equipment need to be improved fordigital broadcast.

SUMMARY OF THE INVENTION

Accordingly, the present invention is directed to an apparatus fortransmitting broadcast signals and an apparatus for receiving broadcastsignals for future broadcast services and methods for transmitting andreceiving broadcast signals for future broadcast services.

An object of the present invention is to provide an apparatus and methodfor transmitting broadcast signals to multiplex data of a broadcasttransmission/reception system providing two or more different broadcastservices in a time domain and transmit the multiplexed data through thesame RF signal bandwidth and an apparatus and method for receivingbroadcast signals corresponding thereto.

Another object of the present invention is to provide an apparatus fortransmitting broadcast signals, an apparatus for receiving broadcastsignals and methods for transmitting and receiving broadcast signals toclassify data corresponding to services by components, transmit datacorresponding to each component as a data pipe, receive and process thedata

Still another object of the present invention is to provide an apparatusfor transmitting broadcast signals, an apparatus for receiving broadcastsignals and methods for transmitting and receiving broadcast signals tosignal signaling information necessary to provide broadcast signals.

To achieve the object and other advantages and in accordance with thepurpose of the invention, as embodied and broadly described herein, thepresent invention provides a method of transmitting broadcast signals.The method of transmitting broadcast signals includes formatting inputstreams into Data Pipe, DP, data; Low-Density Parity-Check, LDPC,encoding the DP data according to a code rate; bit interleaving the LDPCencoded DP data; mapping the bit interleaved DP data onto constellationsaccording to one of QAM (Quadrature Amplitude Modulation), NUQ(Non-Uniform QAM) or NUC (Non-Uniform Constellation); Multi-InputMulti-Output, MIMO, encoding the mapped DP data by using a MIMO encodingmatrix having a MIMO encoding parameter; building at least one signalframe by mapping the MIMO encoded DP data; and modulating data in thebuilt signal frame by an Orthogonal Frequency Division Multiplexing,OFDM, method and transmitting the broadcast signals having the modulateddata.

Preferably, the MIMO encoding is performed according to either FR-SM(Full-rate spatial multiplexing) method or FRFD-SM (Full-rateFull-diversity spatial multiplexing) method.

Preferably, the QAM, the NUQ and the NUC are defined depending on thecode rate. Preferably, the MIMO encoding parameter is defined based onone of the QAM, the NUQ or the NUC.

In other aspect, the present invention provides a method of receivingbroadcast signals. The method of receiving broadcast signals includesreceiving the broadcast signals having at least one signal frame anddemodulating data in the at least one signal frame by an OrthogonalFrequency Division Multiplexing, OFDM, method; parsing the at least onesignal frame by de-mapping Data Pipe, DP, data; Multi-InputMulti-Output, MIMO, decoding the DP data by using a MIMO decoding matrixhaving a MIMO decoding parameter; de-mapping the MIMO decoded DP datafrom constellations according to one of QAM (Quadrature AmplitudeModulation), NUQ (Non-Uniform QAM) or NUC(Non-Uniform Constellation);bit de-interleaving the de-mapped DP data; Low-Density Parity-Check,LDPC, decoding the bit de-interleaved DP data according to a code rate;and de-formatting the LDPC decoded DP data into output streams.

Preferably, the MIMO decoding is performed according to either FR-SM(Full-rate spatial multiplexing) method or FRFD-SM (Full-rateFull-diversity spatial multiplexing) method.

Preferably, the QAM, the NUQ and the NUC are defined depending on thecode rate.

Preferably, the MIMO decoding parameter is defined based on one of theQAM, the NUQ or the NUC.

In another aspect, the present invention provides an apparatus fortransmitting broadcast signals. The apparatus for transmitting broadcastsignals includes a formatting module configured to format input streamsinto Data Pipe, DP, data; a Low-Density Parity-Check, LDPC, encodingmodule configured to LDPC encode the DP data according to a code rate; abit interleaving module configured to bit interleave the LDPC encoded DPdata; a mapping module configured to map the bit interleaved DP dataonto constellations according to one of QAM (Quadrature AmplitudeModulation), NUQ (Non-Uniform QAM) or NUC (Non-Uniform Constellation); aMulti-Input Multi-Output, MIMO, encoding module configured to MIMOencode the mapped DP data by using a MIMO encoding matrix having a MIMOencoding parameter; a frame building module configured to build at leastone signal frame by mapping the MIMO encoded DP data; a modulatingmodule configured to modulate data in the built signal frame by anOrthogonal Frequency Division Multiplexing, OFDM, method; and atransmitting module configured to transmit the broadcast signals havingthe modulated data.

Preferably, the MIMO encoding module performs MIMO encoding according toeither FR-SM (Full-rate spatial multiplexing) method or FRFD-SM(Full-rate Full-diversity spatial multiplexing) method.

Preferably, the QAM, the NUQ and the NUC are defined depending on thecode rate.

Preferably, the MIMO encoding parameter is defined based on one of theQAM, the NUQ or the NUC.

In another aspect, the present invention provides an apparatus forreceiving broadcast signals. The apparatus for receiving broadcastsignals includes a receiving module configured to receive the broadcastsignals having at least one signal frame; a demodulating moduleconfigured to demodulate data in the at least one signal frame by anOrthogonal Frequency Division Multiplexing, OFDM, method; a parsingmodule configured to parse the at least one signal frame by de-mappingData Pipe, DP, data; a Multi-Input Multi-Output, MIMO, decoding moduleconfigured to MIMO decode the DP data by using a MIMO decoding matrixhaving a MIMO decoding parameter; a de-mapping module configured tode-map the MIMO decoded DP data from constellations according to one ofQAM (Quadrature Amplitude Modulation), NUQ (Non-Uniform QAM) or NUC(Non-Uniform Constellation); a bit de-interleaving module configured tobit de-interleave the de-mapped DP data; a Low-Density Parity-Check,LDPC, decoding module configured to LDPC decode the bit de-interleavedDP data according to a code rate; and a de-formatting module configuredto de-format the LDPC decoded DP data into output streams.

Preferably, the MIMO decoding module performs MIMO decoding according toeither FR-SM (Full-rate spatial multiplexing) method or FRFD-SM(Full-rate Full-diversity spatial multiplexing) method.

Preferably, the QAM, the NUQ and the NUC are defined depending on thecode rate.

Preferably, the MIMO decoding parameter is defined based on one of theQAM, the NUQ or the NUC.

The present invention can process data according to servicecharacteristics to control QoS (Quality of Services) for each service orservice component, thereby providing various broadcast services.

The present invention can achieve transmission flexibility bytransmitting various broadcast services through the same RF signalbandwidth.

The present invention can improve data transmission efficiency andincrease robustness of transmission/reception of broadcast signals usinga MIMO system.

According to the present invention, it is possible to provide broadcastsignal transmission and reception methods and apparatus capable ofreceiving digital broadcast signals without error even with mobilereception equipment or in an indoor environment.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings, which are included to provide a furtherunderstanding of the invention and are incorporated in and constitute apart of this application, illustrate embodiment(s) of the invention andtogether with the description serve to explain the principle of theinvention. In the drawings:

FIG. 1 illustrates a structure of an apparatus for transmittingbroadcast signals for future broadcast services according to anembodiment of the present invention.

FIG. 2 illustrates an input formatting block according to one embodimentof the present invention.

FIG. 3 illustrates an input formatting block according to anotherembodiment of the present invention.

FIG. 4 illustrates an input formatting block according to anotherembodiment of the present invention.

FIG. 5 illustrates a BICM block according to an embodiment of thepresent invention.

FIG. 6 illustrates a BICM block according to another embodiment of thepresent invention.

FIG. 7 illustrates a frame building block according to one embodiment ofthe present invention.

FIG. 8 illustrates an OFMD generation block according to an embodimentof the present invention.

FIG. 9 illustrates a structure of an apparatus for receiving broadcastsignals for future broadcast services according to an embodiment of thepresent invention.

FIG. 10 illustrates a frame structure according to an embodiment of thepresent invention.

FIG. 11 illustrates a signaling hierarchy structure of the frameaccording to an embodiment of the present invention.

FIG. 12 illustrates preamble signaling data according to an embodimentof the present invention.

FIG. 13 illustrates PLS1 data according to an embodiment of the presentinvention.

FIG. 14 illustrates PLS2 data according to an embodiment of the presentinvention.

FIG. 15 illustrates PLS2 data according to another embodiment of thepresent invention.

FIG. 16 illustrates a logical structure of a frame according to anembodiment of the present invention.

FIG. 17 illustrates PLS mapping according to an embodiment of thepresent invention.

FIG. 18 illustrates EAC mapping according to an embodiment of thepresent invention.

FIG. 19 illustrates FIC mapping according to an embodiment of thepresent invention.

FIG. 20 illustrates a type of DP according to an embodiment of thepresent invention.

FIG. 21 illustrates DP mapping according to an embodiment of the presentinvention.

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention.

FIG. 23 illustrates a bit interleaving according to an embodiment of thepresent invention.

FIG. 24 illustrates a cell-word demultiplexing according to anembodiment of the present invention.

FIG. 25 illustrates a time interleaving according to an embodiment ofthe present invention.

FIG. 26 illustrates a MIMO encoding block diagram according to anembodiment of the present invention.

FIG. 27 shows a MIMO encoding scheme according to one embodiment of thepresent invention.

FIG. 28 is a diagram showing a PAM grid of an I or Q side according tonon-uniform QAM according to one embodiment of the present invention.

FIG. 29 is a diagram showing MIMO encoding input/output when the PH-eSMPI method is applied to symbols mapped to non-uniform 64 QAM accordingto one embodiment of the present invention.

FIG. 30 is a graph for comparison in performance of MIMO encodingschemes according to the embodiment of the present invention.

FIG. 31 is a graph for comparison in performance of MIMO encodingschemes according to the embodiment of the present invention.

FIG. 32 is a graph for comparison in performance of MIMO encodingschemes according to the embodiment of the present invention.

FIG. 33 is a graph for comparison in performance of MIMO encodingschemes according to the embodiment of the present invention.

FIG. 34 is a diagram showing an embodiment of QAM-16 according to thepresent invention.

FIG. 35 is a diagram showing an embodiment of NUQ-64 for 5/15 code rateaccording to the present invention.

FIG. 36 is a diagram showing an embodiment of NUQ-64 for 6/15 code rateaccording to the present invention.

FIG. 37 is a diagram showing an embodiment of NUQ-64 for 7/15 code rateaccording to the present invention.

FIG. 38 is a diagram showing an embodiment of NUQ-64 for 8/15 code rateaccording to the present invention.

FIG. 39 is a diagram showing an embodiment of NUQ-64 for 9/15 and 10/15code rates according to the present invention.

FIG. 40 is a diagram showing an embodiment of NUQ-64 for 11/15 code rateaccording to the present invention.

FIG. 41 is a diagram showing an embodiment of NUQ-64 for 12/15 code rateaccording to the present invention.

FIG. 42 is a diagram showing an embodiment of NUQ-64 for 13/15 code rateaccording to the present invention.

FIG. 43 is a method of transmitting broadcast signals according to anembodiment of the present invention.

FIG. 44 is a method of receiving broadcast signals according to anembodiment of the present invention.

DETAILED DESCRIPTION OF THE INVENTION

Reference will now be made in detail to the preferred embodiments of thepresent invention, examples of which are illustrated in the accompanyingdrawings. The detailed description, which will be given below withreference to the accompanying drawings, is intended to explain exemplaryembodiments of the present invention, rather than to show the onlyembodiments that can be implemented according to the present invention.The following detailed description includes specific details in order toprovide a thorough understanding of the present invention. However, itwill be apparent to those skilled in the art that the present inventionmay be practiced without such specific details.

Although most terms used in the present invention have been selectedfrom general ones widely used in the art, some terms have beenarbitrarily selected by the applicant and their meanings are explainedin detail in the following description as needed. Thus, the presentinvention should be understood based upon the intended meanings of theterms rather than their simple names or meanings.

The present invention provides apparatuses and methods for transmittingand receiving broadcast signals for future broadcast services. Futurebroadcast services according to an embodiment of the present inventioninclude a terrestrial broadcast service, a mobile broadcast service, aUHDTV service, etc. The present invention may process broadcast signalsfor the future broadcast services through non-MIMO (Multiple InputMultiple Output) or MIMO according to one embodiment. A non-MIMO schemeaccording to an embodiment of the present invention may include a MISO(Multiple Input Single Output) scheme, a SISO (Single Input SingleOutput) scheme, etc.

While MISO or MIMO uses two antennas in the following for convenience ofdescription, the present invention is applicable to systems using two ormore antennas.

The present invention may defines three physical layer (PL)profiles—base, handheld and advanced profiles—each optimized to minimizereceiver complexity while attaining the performance required for aparticular use case. The physical layer (PHY) profiles are subsets ofall configurations that a corresponding receiver should implement.

The three PHY profiles share most of the functional blocks but differslightly in specific blocks and/or parameters. Additional PHY profilescan be defined in the future. For the system evolution, future profilescan also be multiplexed with the existing profiles in a single RFchannel through a future extension frame (FEF). The details of each PHYprofile are described below.

1. Base Profile

The base profile represents a main use case for fixed receiving devicesthat are usually connected to a roof-top antenna. The base profile alsoincludes portable devices that could be transported to a place butbelong to a relatively stationary reception category. Use of the baseprofile could be extended to handheld devices or even vehicular by someimproved implementations, but those use cases are not expected for thebase profile receiver operation.

Target SNR range of reception is from approximately 10 to 20 dB, whichincludes the 15 dB SNR reception capability of the existing broadcastsystem (e.g. ATSC A/53). The receiver complexity and power consumptionis not as critical as in the battery-operated handheld devices, whichwill use the handheld profile. Key system parameters for the baseprofile are listed in below table 1.

TABLE 1 LDPC codeword length 16K, 64K bits Constellation size 4~10 bpcu(bits per channel use) Time de-interleaving memory size ≦2¹⁹ data cellsPilot patterns Pilot pattern for fixed reception FFT size 16K, 32Kpoints

2. Handheld Profile

The handheld profile is designed for use in handheld and vehiculardevices that operate with battery power. The devices can be moving withpedestrian or vehicle speed. The power consumption as well as thereceiver complexity is very important for the implementation of thedevices of the handheld profile. The target SNR range of the handheldprofile is approximately 0 to 10 dB, but can be configured to reachbelow 0 dB when intended for deeper indoor reception.

In addition to low SNR capability, resilience to the Doppler Effectcaused by receiver mobility is the most important performance attributeof the handheld profile. Key system parameters for the handheld profileare listed in the below table 2.

TABLE 2 LDPC codeword length 16K bits Constellation size 2~8 bpcu Timede-interleaving memory size ≦2¹⁸ data cells Pilot patterns Pilotpatterns for mobile and indoor reception FFT size 8K, 16K points

3. Advanced Profile

The advanced profile provides highest channel capacity at the cost ofmore implementation complexity. This profile requires using MIMOtransmission and reception, and UHDTV service is a target use case forwhich this profile is specifically designed. The increased capacity canalso be used to allow an increased number of services in a givenbandwidth, e.g., multiple SDTV or HDTV services.

The target SNR range of the advanced profile is approximately 20 to 30dB. MIMO transmission may initially use existing elliptically-polarizedtransmission equipment, with extension to full-power cross-polarizedtransmission in the future. Key system parameters for the advancedprofile are listed in below table 3.

TABLE 3 LDPC codeword length 16K, 64K bits Constellation size 8~12 bpcuTime de-interleaving memory size ≦2¹⁹ data cells Pilot patterns Pilotpattern for fixed reception FFT size 16K, 32K points

FIG. 1 illustrates a structure of an apparatus for transmittingbroadcast signals for future broadcast services according to anembodiment of the present invention.

The apparatus for transmitting broadcast signals for future broadcastservices according to an embodiment of the present invention can includean input formatting block 1000, a BICM (Bit interleaved coding &modulation) block 1010, a frame structure block 1020, an OFDM(Orthogonal Frequency Division Multiplexing) generation block 1030 and asignaling generation block 1040. A description will be given of theoperation of each module of the apparatus for transmitting broadcastsignals.

IP stream/packets and MPEG2-TS are the main input formats, other streamtypes are handled as General Streams. In addition to these data inputs,Management Information is input to control the scheduling and allocationof the corresponding bandwidth for each input stream. One or multiple TSstream(s), IP stream(s) and/or General Stream(s) inputs aresimultaneously allowed.

The input formatting block 1000 can demultiplex each input stream intoone or multiple data pipe(s), to each of which an independent coding andmodulation is applied. The data pipe (DP) is the basic unit forrobustness control, thereby affecting quality-of-service (QoS). One ormultiple service(s) or service component(s) can be carried by a singleDP. Details of operations of the input formatting block 1000 will bedescribed later.

The data pipe is a logical channel in the physical layer that carriesservice data or related metadata, which may carry one or multipleservice(s) or service component(s).

Also, the data pipe unit: a basic unit for allocating data cells to a DPin a frame. In the BICM block 1010, parity data is added for errorcorrection and the encoded bit streams are mapped to complex-valueconstellation symbols. The symbols are interleaved across a specificinterleaving depth that is used for the corresponding DP. For theadvanced profile, MIMO encoding is performed in the BICM block 1010 andthe additional data path is added at the output for MIMO transmission.Details of operations of the BICM block 1010 will be described later.

The Frame Building block 1020 can map the data cells of the input DPsinto the OFDM symbols within a frame. After mapping, the frequencyinterleaving is used for frequency-domain diversity, especially tocombat frequency-selective fading channels. Details of operations of theFrame Building block 1020 will be described later.

After inserting a preamble at the beginning of each frame, the OFDMGeneration block 1030 can apply conventional OFDM modulation having acyclic prefix as guard interval. For antenna space diversity, adistributed MISO scheme is applied across the transmitters. In addition,a Peak-to-Average Power Reduction (PAPR) scheme is performed in the timedomain. For flexible network planning, this proposal provides a set ofvarious FFT sizes, guard interval lengths and corresponding pilotpatterns. Details of operations of the OFDM Generation block 1030 willbe described later.

The Signaling Generation block 1040 can create physical layer signalinginformation used for the operation of each functional block. Thissignaling information is also transmitted so that the services ofinterest are properly recovered at the receiver side. Details ofoperations of the Signaling Generation block 1040 will be describedlater.

FIGS. 2, 3 and 4 illustrate the input formatting block 1000 according toembodiments of the present invention. A description will be given ofeach figure.

FIG. 2 illustrates an input formatting block according to one embodimentof the present invention. FIG. 2 shows an input formatting module whenthe input signal is a single input stream.

The input formatting block illustrated in FIG. 2 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

The input to the physical layer may be composed of one or multiple datastreams. Each data stream is carried by one DP. The mode adaptationmodules slice the incoming data stream into data fields of the basebandframe (BBF). The system supports three types of input data streams:MPEG2-TS, Internet protocol (IP) and Generic stream (GS). MPEG2-TS ischaracterized by fixed length (188 byte) packets with the first bytebeing a sync-byte (0x47). An IP stream is composed of variable length IPdatagram packets, as signaled within IP packet headers. The systemsupports both IPv4 and IPv6 for the IP stream. GS may be composed ofvariable length packets or constant length packets, signaled withinencapsulation packet headers.

(a) shows a mode adaptation block 2000 and a stream adaptation 2010 forsignal DP and (b) shows a PLS generation block 2020 and a PLS scrambler2030 for generating and processing PLS data. A description will be givenof the operation of each block.

The Input Stream Splitter splits the input TS, IP, GS streams intomultiple service or service component (audio, video, etc.) streams. Themode adaptation module 2010 is comprised of a CRC Encoder, BB (baseband)Frame Slicer, and BB Frame Header Insertion block.

The CRC Encoder provides three kinds of CRC encoding for error detectionat the user packet (UP) level, i.e., CRC-8, CRC-16, and CRC-32. Thecomputed CRC bytes are appended after the UP. CRC-8 is used for TSstream and CRC-32 for IP stream. If the GS stream doesn't provide theCRC encoding, the proposed CRC encoding should be applied.

BB Frame Slicer maps the input into an internal logical-bit format. Thefirst received bit is defined to be the MSB. The BB Frame Slicerallocates a number of input bits equal to the available data fieldcapacity. To allocate a number of input bits equal to the BBF payload,the UP packet stream is sliced to fit the data field of BBF.

BB Frame Header Insertion block can insert fixed length BBF header of 2bytes is inserted in front of the BB Frame. The BBF header is composedof STUFFI (1 bit), SYNCD (13 bits), and RFU (2 bits). In addition to thefixed 2-Byte BBF header, BBF can have an extension field (1 or 3 bytes)at the end of the 2-byte BBF header.

The stream adaptation 2010 is comprised of stuffing insertion block andBB scrambler.

The stuffing insertion block can insert stuffing field into a payload ofa BB frame. If the input data to the stream adaptation is sufficient tofill a BB-Frame, STUFFI is set to ‘0’ and the BBF has no stuffing field.Otherwise STUFFI is set to ‘1’ and the stuffing field is insertedimmediately after the BBF header. The stuffing field comprises two bytesof the stuffing field header and a variable size of stuffing data.

The BB scrambler scrambles complete BBF for energy dispersal. Thescrambling sequence is synchronous with the BBF. The scrambling sequenceis generated by the feed-back shift register.

The PLS generation block 2020 can generate physical layer signaling(PLS) data. The PLS provides the receiver with a means to accessphysical layer DPs. The PLS data consists of PLS1 data and PLS2 data.

The PLS1 data is a first set of PLS data carried in the FSS symbols inthe frame having a fixed size, coding and modulation, which carriesbasic information about the system as well as the parameters needed todecode the PLS2 data. The PLS1 data provides basic transmissionparameters including parameters required to enable the reception anddecoding of the PLS2 data. Also, the PLS1 data remains constant for theduration of a frame-group.

The PLS2 data is a second set of PLS data transmitted in the FSS symbol,which carries more detailed PLS data about the system and the DPs. ThePLS2 contains parameters that provide sufficient information for thereceiver to decode the desired DP. The PLS2 signaling further consistsof two types of parameters, PLS2 Static data (PLS2-STAT data) and PLS2dynamic data (PLS2-DYN data). The PLS2 Static data is PLS2 data thatremains static for the duration of a frame-group and the PLS2 dynamicdata is PLS2 data that may dynamically change frame-by-frame.

Details of the PLS data will be described later.

The PLS scrambler 2030 can scramble the generated PLS data for energydispersal.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 3 illustrates an input formatting block according to anotherembodiment of the present invention.

The input formatting block illustrated in FIG. 3 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

FIG. 3 shows a mode adaptation block of the input formatting block whenthe input signal corresponds to multiple input streams.

The mode adaptation block of the input formatting block for processingthe multiple input streams can independently process the multiple inputstreams.

Referring to FIG. 3, the mode adaptation block for respectivelyprocessing the multiple input streams can include an input streamsplitter 3000, an input stream synchronizer 3010, a compensating delayblock 3020, a null packet deletion block 3030, a head compression block3040, a CRC encoder 3050, a BB frame slicer 3060 and a BB headerinsertion block 3070. Description will be given of each block of themode adaptation block.

Operations of the CRC encoder 3050, BB frame slicer 3060 and BB headerinsertion block 3070 correspond to those of the CRC encoder, BB frameslicer and BB header insertion block described with reference to FIG. 2and thus description thereof is omitted.

The input stream splitter 3000 can split the input TS, IP, GS streamsinto multiple service or service component (audio, video, etc.) streams.

The input stream synchronizer 3010 may be referred as ISSY. The ISSY canprovide suitable means to guarantee Constant Bit Rate (CBR) and constantend-to-end transmission delay for any input data format. The ISSY isalways used for the case of multiple DPs carrying TS, and optionallyused for multiple DPs carrying GS streams.

The compensating delay block 3020 can delay the split TS packet streamfollowing the insertion of ISSY information to allow a TS packetrecombining mechanism without requiring additional memory in thereceiver.

The null packet deletion block 3030, is used only for the TS inputstream case. Some TS input streams or split TS streams may have a largenumber of null-packets present in order to accommodate VBR (variablebit-rate) services in a CBR TS stream. In this case, in order to avoidunnecessary transmission overhead, null-packets can be identified andnot transmitted. In the receiver, removed null-packets can bere-inserted in the exact place where they were originally by referenceto a deleted null-packet (DNP) counter that is inserted in thetransmission, thus guaranteeing constant bit-rate and avoiding the needfor time-stamp (PCR) updating.

The head compression block 3040 can provide packet header compression toincrease transmission efficiency for TS or IP input streams. Because thereceiver can have a priori information on certain parts of the header,this known information can be deleted in the transmitter.

For Transport Stream, the receiver has a-priori information about thesync-byte configuration (0x47) and the packet length (188 Byte). If theinput TS stream carries content that has only one PID, i.e., for onlyone service component (video, audio, etc.) or service sub-component (SVCbase layer, SVC enhancement layer, MVC base view or MVC dependentviews), TS packet header compression can be applied (optionally) to theTransport Stream. IP packet header compression is used optionally if theinput steam is an IP stream.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 4 illustrates an input formatting block according to anotherembodiment of the present invention.

The input formatting block illustrated in FIG. 4 corresponds to anembodiment of the input formatting block 1000 described with referenceto FIG. 1.

FIG. 4 illustrates a stream adaptation block of the input formattingmodule when the input signal corresponds to multiple input streams.

Referring to FIG. 4, the mode adaptation block for respectivelyprocessing the multiple input streams can include a scheduler 4000, an1-Frame delay block 4010, a stuffing insertion block 4020, an in-bandsignaling 4030, a BB Frame scrambler 4040, a PLS generation block 4050and a PLS scrambler 4060. Description will be given of each block of thestream adaptation block.

Operations of the stuffing insertion block 4020, the BB Frame scrambler4040, the PLS generation block 4050 and the PLS scrambler 4060correspond to those of the stuffing insertion block, BB scrambler, PLSgeneration block and the PLS scrambler described with reference to FIG.2 and thus description thereof is omitted.

The scheduler 4000 can determine the overall cell allocation across theentire frame from the amount of FECBLOCKs of each DP. Including theallocation for PLS, EAC and FIC, the scheduler generate the values ofPLS2-DYN data, which is transmitted as in-band signaling or PLS cell inFSS of the frame. Details of FECBLOCK, EAC and FIC will be describedlater.

The 1-Frame delay block 4010 can delay the input data by onetransmission frame such that scheduling information about the next framecan be transmitted through the current frame for in-band signalinginformation to be inserted into the DPs.

The in-band signaling 4030 can insert un-delayed part of the PLS2 datainto a DP of a frame.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 5 illustrates a BICM block according to an embodiment of thepresent invention.

The BICM block illustrated in FIG. 5 corresponds to an embodiment of theBICM block 1010 described with reference to FIG. 1.

As described above, the apparatus for transmitting broadcast signals forfuture broadcast services according to an embodiment of the presentinvention can provide a terrestrial broadcast service, mobile broadcastservice, UHDTV service, etc.

Since QoS (quality of service) depends on characteristics of a serviceprovided by the apparatus for transmitting broadcast signals for futurebroadcast services according to an embodiment of the present invention,data corresponding to respective services needs to be processed throughdifferent schemes. Accordingly, the a BICM block according to anembodiment of the present invention can independently process DPs inputthereto by independently applying SISO, MISO and MIMO schemes to thedata pipes respectively corresponding to data paths. Consequently, theapparatus for transmitting broadcast signals for future broadcastservices according to an embodiment of the present invention can controlQoS for each service or service component transmitted through each DP.

(a) shows the BICM block shared by the base profile and the handheldprofile and (b) shows the BICM block of the advanced profile.

The BICM block shared by the base profile and the handheld profile andthe BICM block of the advanced profile can include plural processingblocks for processing each DP.

A description will be given of each processing block of the BICM blockfor the base profile and the handheld profile and the BICM block for theadvanced profile.

A processing block 5000 of the BICM block for the base profile and thehandheld profile can include a Data FEC encoder 5010, a bit interleaver5020, a constellation mapper 5030, an SSD (Signal Space Diversity)encoding block 5040 and a time interleaver 5050.

The Data FEC encoder 5010 can perform the FEC encoding on the input BBFto generate FECBLOCK procedure using outer coding (BCH), and innercoding (LDPC). The outer coding (BCH) is optional coding method. Detailsof operations of the Data FEC encoder 5010 will be described later.

The bit interleaver 5020 can interleave outputs of the Data FEC encoder5010 to achieve optimized performance with combination of the LDPC codesand modulation scheme while providing an efficiently implementablestructure. Details of operations of the bit interleaver 5020 will bedescribed later.

The constellation mapper 5030 can modulate each cell word from the bitinterleaver 5020 in the base and the handheld profiles, or cell wordfrom the Cell-word demultiplexer 5010-1 in the advanced profile usingeither QPSK, QAM-16, non-uniform QAM (NUQ-64, NUQ-256, NUQ-1024) ornon-uniform constellation (NUC-16, NUC-64, NUC-256, NUC-1024) to give apower-normalized constellation point, e_(l). This constellation mappingis applied only for DPs. Observe that QAM-16 and NUQs are square shaped,while NUCs have arbitrary shape. When each constellation is rotated byany multiple of 90 degrees, the rotated constellation exactly overlapswith its original one. This “rotation-sense” symmetric property makesthe capacities and the average powers of the real and imaginarycomponents equal to each other. Both NUQs and NUCs are definedspecifically for each code rate and the particular one used is signaledby the parameter DP_MOD filed in PLS2 data.

The SSD encoding block 5040 can precode cells in two (2D), three (3D),and four (4D) dimensions to increase the reception robustness underdifficult fading conditions.

The time interleaver 5050 can operates at the DP level. The parametersof time interleaving (TI) may be set differently for each DP. Details ofoperations of the time interleaver 5050 will be described later.

A processing block 5000-1 of the BICM block for the advanced profile caninclude the Data FEC encoder, bit interleaver, constellation mapper, andtime interleaver. However, the processing block 5000-1 is distinguishedfrom the processing block 5000 further includes a cell-worddemultiplexer 5010-1 and a MIMO encoding block 5020-1.

Also, the operations of the Data FEC encoder, bit interleaver,constellation mapper, and time interleaver in the processing block5000-1 correspond to those of the Data FEC encoder 5010, bit interleaver5020, constellation mapper 5030, and time interleaver 5050 described andthus description thereof is omitted.

The cell-word demultiplexer 5010-1 is used for the DP of the advancedprofile to divide the single cell-word stream into dual cell-wordstreams for MIMO processing. Details of operations of the cell-worddemultiplexer 5010-1 will be described later.

The MIMO encoding block 5020-1 can processing the output of thecell-word demultiplexer 5010-1 using MIMO encoding scheme. The MIMOencoding scheme was optimized for broadcasting signal transmission. TheMIMO technology is a promising way to get a capacity increase but itdepends on channel characteristics. Especially for broadcasting, thestrong LOS component of the channel or a difference in the receivedsignal power between two antennas caused by different signal propagationcharacteristics makes it difficult to get capacity gain from MIMO. Theproposed MIMO encoding scheme overcomes this problem using arotation-based pre-coding and phase randomization of one of the MIMOoutput signals.

MIMO encoding is intended for a 2×2 MIMO system requiring at least twoantennas at both the transmitter and the receiver. Two MIMO encodingmodes are defined in this proposal; full-rate spatial multiplexing(FR-SM) and full-rate full-diversity spatial multiplexing (FRFD-SM). TheFR-SM encoding provides capacity increase with relatively smallcomplexity increase at the receiver side while the FRFD-SM encodingprovides capacity increase and additional diversity gain with a greatcomplexity increase at the receiver side. The proposed MIMO encodingscheme has no restriction on the antenna polarity configuration.

MIMO processing is required for the advanced profile frame, which meansall DPs in the advanced profile frame are processed by the MIMO encoder.MIMO processing is applied at DP level. Pairs of the ConstellationMapper outputs NUQ (e_(1,i) and e_(2,i)) are fed to the input of theMIMO Encoder. Paired MIMO Encoder output (g1,i and g2,i) is transmittedby the same carrier k and OFDM symbol l of their respective TX antennas.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 6 illustrates a BICM block according to another embodiment of thepresent invention.

The BICM block illustrated in FIG. 6 corresponds to an embodiment of theBICM block 1010 described with reference to FIG. 1.

FIG. 6 illustrates a BICM block for protection of physical layersignaling (PLS), emergency alert channel (EAC) and fast informationchannel (FIC). EAC is a part of a frame that carries EAS informationdata and FIC is a logical channel in a frame that carries the mappinginformation between a service and the corresponding base DP. Details ofthe EAC and FIC will be described later.

Referring to FIG. 6, the BICM block for protection of PLS, EAC and FICcan include a PLS FEC encoder 6000, a bit interleaver 6010, aconstellation mapper 6020 and time interleaver 6030.

Also, the PLS FEC encoder 6000 can include a scrambler, BCHencoding/zero insertion block, LDPC encoding block and LDPC paritypunturing block. Description will be given of each block of the BICMblock.

The PLS FEC encoder 6000 can encode the scrambled PLS1/2 data, EAC andFIC section.

The scrambler can scramble PLS1 data and PLS2 data before BCH encodingand shortened and punctured LDPC encoding.

The BCH encoding/zero insertion block can perform outer encoding on thescrambled PLS1/2 data using the shortened BCH code for PLS protectionand insert zero bits after the BCH encoding. For PLS1 data only, theoutput bits of the zero insertion may be permutted before LDPC encoding.

The LDPC encoding block can encode the output of the BCH encoding/zeroinsertion block using LDPC code. To generate a complete coded block,C_(ldpc), parity bits, P_(ldpc) are encoded systematically from eachzero-inserted PLS information block, I_(ldpc) and appended after it.C _(ldpc) =[I _(ldpc) P _(ldpc) ]=[i ₀ ,i ₁ , . . . i _(K) _(lpdc) ₋₁ ,p₀ ,p ₁ , . . . , p _(N) _(lpdc) _(-K) _(lpdc) ₋₁]  [Expression 1]

The LDPC code parameters for PLS1 and PLS2 are as following table 4.

TABLE 4 Signaling K_(ldpc) code Type K_(sig) K_(bch) N_(bch) _(—)_(parity) (=N_(bch)) N_(ldpc) N_(ldpc) _(—) _(parity) rate Q_(ldpc) PLS1342 1020 60 1080 4320 3240 1/4  36 PLS2 <1021 >1020 2100 2160 7200 50403/10 56

The LDPC parity punturing block can perform puncturing on the PLS1 dataand PLS 2 data.

When shortening is applied to the PLS1 data protection, some LDPC paritybits are punctured after LDPC encoding. Also, for the PLS2 dataprotection, the LDPC parity bits of PLS2 are punctured after LDPCencoding. These punctured bits are not transmitted.

The bit interleaver 6010 can interleave the each shortened and puncturedPLS1 data and PLS2 data.

The constellation mapper 6020 can map the bit interleaved PLS1 data andPLS2 data onto constellations.

The time interleaver 6030 can interleave the mapped PLS1 data and PLS2data.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 7 illustrates a frame building block according to one embodiment ofthe present invention.

The frame building block illustrated in FIG. 7 corresponds to anembodiment of the frame building block 1020 described with reference toFIG. 1.

Referring to FIG. 7, the frame building block can include a delaycompensation block 7000, a cell mapper 7010 and a frequency interleaver7020. Description will be given of each block of the frame buildingblock.

The delay compensation block 7000 can adjust the timing between the datapipes and the corresponding PLS data to ensure that they are co-timed atthe transmitter end. The PLS data is delayed by the same amount as datapipes are by addressing the delays of data pipes caused by the InputFormatting block and BICM block. The delay of the BICM block is mainlydue to the time interleaver. In-band signaling data carries informationof the next TI group so that they are carried one frame ahead of the DPsto be signaled. The Delay Compensating block delays in-band signalingdata accordingly.

The cell mapper 7010 can map PLS, EAC, FIC, DPs, auxiliary streams anddummy cells into the active carriers of the OFDM symbols in the frame.Details of the frame will be described later.

The frequency interleaver 7020 can randomly interleave data cellsreceived from the cell mapper 7010 to provide frequency diversity. Also,the frequency interleaver 7020 can operate on very OFDM symbol paircomprised of two sequential OFDM symbols using a differentinterleaving-seed order to get maximum interleaving gain in a singleframe. Details of operations of the frequency interleaver 7020 will bedescribed later.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 8 illustrates an OFMD generation block according to an embodimentof the present invention.

The OFMD generation block illustrated in FIG. 8 corresponds to anembodiment of the OFMD generation block 1030 described with reference toFIG. 1.

The OFDM generation block modulates the OFDM carriers by the cellsproduced by the Frame Building block, inserts the pilots, and producesthe time domain signal for transmission. Also, this block subsequentlyinserts guard intervals, and applies PAPR (Peak-to-Average Power Radio)reduction processing to produce the final RF signal.

Referring to FIG. 8, the frame building block can include a pilot andreserved tone insertion block 8000, a 2D-eSFN encoding block 8010, anIFFT (Inverse Fast Fourier Transform) block 8020, a PAPR reduction block8030, a guard interval insertion block 8040, a preamble insertion block8050, other system insertion block 8060 and a DAC block 8070.Description will be given of each block of the frame building block.

The pilot and reserved tone insertion block 8000 can insert pilots andthe reserved tone.

Various cells within the OFDM symbol are modulated with referenceinformation, known as pilots, which have transmitted values known apriori in the receiver. The information of pilot cells is made up ofscattered pilots, continual pilots, edge pilots, FSS (frame signalingsymbol) pilots and FES (frame edge symbol) pilots. Each pilot istransmitted at a particular boosted power level according to pilot typeand pilot pattern. The value of the pilot information is derived from areference sequence, which is a series of values, one for eachtransmitted carrier on any given symbol. The pilots can be used forframe synchronization, frequency synchronization, time synchronization,channel estimation, and transmission mode identification, and also canbe used to follow the phase noise.

Reference information, taken from the reference sequence, is transmittedin scattered pilot cells in every symbol except the preamble, FSS andFES of the frame. Continual pilots are inserted in every symbol of theframe. The number and location of continual pilots depends on both theFFT size and the scattered pilot pattern. The edge carriers are edgepilots in every symbol except for the preamble symbol. They are insertedin order to allow frequency interpolation up to the edge of thespectrum. FSS pilots are inserted in FSS(s) and FES pilots are insertedin FES. They are inserted in order to allow time interpolation up to theedge of the frame.

The system according to an embodiment of the present invention supportsthe SFN network, where distributed MISO scheme is optionally used tosupport very robust transmission mode. The 2D-eSFN is a distributed MISOscheme that uses multiple TX antennas, each of which is located in thedifferent transmitter site in the SFN network.

The 2D-eSFN encoding block 8010 can process a 2D-eSFN processing todistorts the phase of the signals transmitted from multipletransmitters, in order to create both time and frequency diversity inthe SFN configuration. Hence, burst errors due to low flat fading ordeep-fading for a long time can be mitigated.

The IFFT block 8020 can modulate the output from the 2D-eSFN encodingblock 8010 using OFDM modulation scheme. Any cell in the data symbolswhich has not been designated as a pilot (or as a reserved tone) carriesone of the data cells from the frequency interleaver. The cells aremapped to OFDM carriers.

The PAPR reduction block 8030 can perform a PAPR reduction on inputsignal using various PAPR reduction algorithm in the time domain.

The guard interval insertion block 8040 can insert guard intervals andthe preamble insertion block 8050 can insert preamble in front of thesignal. Details of a structure of the preamble will be described later.The other system insertion block 8060 can multiplex signals of aplurality of broadcast transmission/reception systems in the time domainsuch that data of two or more different broadcast transmission/receptionsystems providing broadcast services can be simultaneously transmittedin the same RF signal bandwidth. In this case, the two or more differentbroadcast transmission/reception systems refer to systems providingdifferent broadcast services. The different broadcast services may referto a terrestrial broadcast service, mobile broadcast service, etc. Datarelated to respective broadcast services can be transmitted throughdifferent frames.

The DAC block 8070 can convert an input digital signal into an analogsignal and output the analog signal. The signal output from the DACblock 7800 can be transmitted through multiple output antennas accordingto the physical layer profiles. A Tx antenna according to an embodimentof the present invention can have vertical or horizontal polarity.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

FIG. 9 illustrates a structure of an apparatus for receiving broadcastsignals for future broadcast services according to an embodiment of thepresent invention.

The apparatus for receiving broadcast signals for future broadcastservices according to an embodiment of the present invention cancorrespond to the apparatus for transmitting broadcast signals forfuture broadcast services, described with reference to FIG. 1.

The apparatus for receiving broadcast signals for future broadcastservices according to an embodiment of the present invention can includea synchronization & demodulation module 9000, a frame parsing module9010, a demapping & decoding module 9020, an output processor 9030 and asignaling decoding module 9040. A description will be given of operationof each module of the apparatus for receiving broadcast signals.

The synchronization & demodulation module 9000 can receive input signalsthrough m Rx antennas, perform signal detection and synchronization withrespect to a system corresponding to the apparatus for receivingbroadcast signals and carry out demodulation corresponding to a reverseprocedure of the procedure performed by the apparatus for transmittingbroadcast signals.

The frame parsing module 9100 can parse input signal frames and extractdata through which a service selected by a user is transmitted. If theapparatus for transmitting broadcast signals performs interleaving, theframe parsing module 9100 can carry out deinterleaving corresponding toa reverse procedure of interleaving. In this case, the positions of asignal and data that need to be extracted can be obtained by decodingdata output from the signaling decoding module 9400 to restorescheduling information generated by the apparatus for transmittingbroadcast signals.

The demapping & decoding module 9200 can convert the input signals intobit domain data and then deinterleave the same as necessary. Thedemapping & decoding module 9200 can perform demapping for mappingapplied for transmission efficiency and correct an error generated on atransmission channel through decoding. In this case, the demapping &decoding module 9200 can obtain transmission parameters necessary fordemapping and decoding by decoding the data output from the signalingdecoding module 9400.

The output processor 9300 can perform reverse procedures of variouscompression/signal processing procedures which are applied by theapparatus for transmitting broadcast signals to improve transmissionefficiency. In this case, the output processor 9300 can acquirenecessary control information from data output from the signalingdecoding module 9400. The output of the output processor 8300corresponds to a signal input to the apparatus for transmittingbroadcast signals and may be MPEG-TSs, IP streams (v4 or v6) and genericstreams.

The signaling decoding module 9400 can obtain PLS information from thesignal demodulated by the synchronization & demodulation module 9000. Asdescribed above, the frame parsing module 9100, demapping & decodingmodule 9200 and output processor 9300 can execute functions thereofusing the data output from the signaling decoding module 9400.

FIG. 10 illustrates a frame structure according to an embodiment of thepresent invention.

FIG. 10 shows an example configuration of the frame types and FRUs in asuper-frame. (a) shows a super frame according to an embodiment of thepresent invention, (b) shows FRU (Frame Repetition Unit) according to anembodiment of the present invention, (c) shows frames of variable PHYprofiles in the FRU and (d) shows a structure of a frame.

A super-frame may be composed of eight FRUs. The FRU is a basicmultiplexing unit for TDM of the frames, and is repeated eight times ina super-frame.

Each frame in the FRU belongs to one of the PHY profiles, (base,handheld, advanced) or FEF. The maximum allowed number of the frames inthe FRU is four and a given PHY profile can appear any number of timesfrom zero times to four times in the FRU (e.g., base, base, handheld,advanced). PHY profile definitions can be extended using reserved valuesof the PHY_PROFILE in the preamble, if required.

The FEF part is inserted at the end of the FRU, if included. When theFEF is included in the FRU, the minimum number of FEFs is 8 in asuper-frame. It is not recommended that FEF parts be adjacent to eachother.

One frame is further divided into a number of OFDM symbols and apreamble. As shown in (d), the frame comprises a preamble, one or moreframe signaling symbols (FSS), normal data symbols and a frame edgesymbol (FES).

The preamble is a special symbol that enables fast Futurecast UTB systemsignal detection and provides a set of basic transmission parameters forefficient transmission and reception of the signal. The detaileddescription of the preamble will be will be described later.

The main purpose of the FSS(s) is to carry the PLS data. For fastsynchronization and channel estimation, and hence fast decoding of PLSdata, the FSS has more dense pilot pattern than the normal data symbol.The FES has exactly the same pilots as the FSS, which enablesfrequency-only interpolation within the FES and temporal interpolation,without extrapolation, for symbols immediately preceding the FES.

FIG. 11 illustrates a signaling hierarchy structure of the frameaccording to an embodiment of the present invention.

FIG. 11 illustrates the signaling hierarchy structure, which is splitinto three main parts: the preamble signaling data 11000, the PLS1 data11010 and the PLS2 data 11020. The purpose of the preamble, which iscarried by the preamble symbol in every frame, is to indicate thetransmission type and basic transmission parameters of that frame. ThePLS1 enables the receiver to access and decode the PLS2 data, whichcontains the parameters to access the DP of interest. The PLS2 iscarried in every frame and split into two main parts: PLS2-STAT data andPLS2-DYN data. The static and dynamic portion of PLS2 data is followedby padding, if necessary.

FIG. 12 illustrates preamble signaling data according to an embodimentof the present invention.

Preamble signaling data carries 21 bits of information that are neededto enable the receiver to access PLS data and trace DPs within the framestructure. Details of the preamble signaling data are as follows:

PHY_PROFILE: This 3-bit field indicates the PHY profile type of thecurrent frame. The mapping of different PHY profile types is given inbelow table 5.

TABLE 5 Value PHY profile 000 Base profile 001 Handheld profile 010Advanced profiled 011~110 Reserved 111 FEF

FFT_SIZE: This 2 bit field indicates the FFT size of the current framewithin a frame-group, as described in below table 6.

TABLE 6 Value FFT size 00  8K FFT 01 16K FFT 10 32K FFT 11 Reserved

GI_FRACTION: This 3 bit field indicates the guard interval fractionvalue in the current super-frame, as described in below table 7.

TABLE 7 Value GI_FRACTION 000 1/5  001 1/10 010 1/20 011 1/40 100 1/80101  1/160 110~111 Reserved

EAC_FLAG: This 1 bit field indicates whether the EAC is provided in thecurrent frame. If this field is set to ‘1’, emergency alert service(EAS) is provided in the current frame. If this field set to ‘0’, EAS isnot carried in the current frame. This field can be switched dynamicallywithin a super-frame.

PILOT_MODE: This 1-bit field indicates whether the pilot mode is mobilemode or fixed mode for the current frame in the current frame-group. Ifthis field is set to ‘0’, mobile pilot mode is used. If the field is setto ‘1’, the fixed pilot mode is used.

PAPR_FLAG: This 1-bit field indicates whether PAPR reduction is used forthe current frame in the current frame-group. If this field is set tovalue ‘1’, tone reservation is used for PAPR reduction. If this field isset to ‘0’, PAPR reduction is not used.

FRU_CONFIGURE: This 3-bit field indicates the PHY profile typeconfigurations of the frame repetition units (FRU) that are present inthe current super-frame. All profile types conveyed in the currentsuper-frame are identified in this field in all preambles in the currentsuper-frame. The 3-bit field has a different definition for eachprofile, as show in below table 8.

TABLE 8 Current Current Current Current PHY_PROFILE = PHY_PROFILE =PHY_PROFILE = PHY_PROFILE = ‘000’ (base) ‘001’ (handheld) ‘010’(advanced) ‘111’ (FEF) FRU_CONFIGURE = Only base Only handheld Onlyadvanced Only FEF 000 profile present profile present profile presentpresent FRU_CONFIGURE = Handheld Base profile Base profile Base profile1XX profile present present present present FRU_CONFIGURE = AdvancedAdvanced Handheld Handheld X1X profile present profile present profilepresent profile present FRU_CONFIGURE = FEF FEF FEF Advanced XX1 presentpresent present profile present

FIG. 13 illustrates PLS1 data according to an embodiment of the presentinvention. PLS1 data provides basic transmission parameters includingparameters required to enable the reception and decoding of the PLS2. Asabove mentioned, the PLS1 data remain unchanged for the entire durationof one frame-group. The detailed definition of the signaling fields ofthe PLS1 data are as follows:

PREAMBLE_DATA: This 20-bit field is a copy of the preamble signalingdata excluding the EAC_FLAG.

NUM_FRAME_FRU: This 2-bit field indicates the number of the frames perFRU.

PAYLOAD_TYPE: This 3-bit field indicates the format of the payload datacarried in the frame-group. PAYLOAD_TYPE is signaled as shown in table9.

TABLE 9 value Payload type 1XX TS stream is transmitted X1X IP stream istransmitted XX1 GS stream is transmitted

NUM_FSS: This 2-bit field indicates the number of FSS symbols in thecurrent frame.

SYSTEM_VERSION: This 8-bit field indicates the version of thetransmitted signal format. The SYSTEM_VERSION is divided into two 4-bitfields, which are a major version and a minor version.

Major version: The MSB four bits of SYSTEM_VERSION field indicate majorversion information. A change in the major version field indicates anon-backward-compatible change. The default value is ‘0000’. For theversion described in this standard, the value is set to ‘0000’.

Minor version: The LSB four bits of SYSTEM_VERSION field indicate minorversion information. A change in the minor version field isbackward-compatible.

CELL_ID: This is a 16-bit field which uniquely identifies a geographiccell in an ATSC network. An ATSC cell coverage area may consist of oneor more frequencies, depending on the number of frequencies used perFuturecast UTB system. If the value of the CELL_ID is not known orunspecified, this field is set to ‘0’.

NETWORK_ID: This is a 16-bit field which uniquely identifies the currentATSC network.

SYSTEM_ID: This 16-bit field uniquely identifies the Futurecast UTBsystem within the ATSC network. The Futurecast UTB system is theterrestrial broadcast system whose input is one or more input streams(TS, IP, GS) and whose output is an RF signal. The Futurecast UTB systemcarries one or more PHY profiles and FEF, if any. The same FuturecastUTB system may carry different input streams and use different RFfrequencies in different geographical areas, allowing local serviceinsertion. The frame structure and scheduling is controlled in one placeand is identical for all transmissions within a Futurecast UTB system.One or more Futurecast UTB systems may have the same SYSTEM_ID meaningthat they all have the same physical layer structure and configuration.

The following loop consists of FRU⁺ PHY_PROFILE, FRU_FRAME_LENGTH,FRU_GI_FRACTION, and RESERVED which are used to indicate the FRUconfiguration and the length of each frame type. The loop size is fixedso that four PHY profiles (including a FEF) are signaled within the FRU.If NUM_FRAME_FRU is less than 4, the unused fields are filled withzeros.

FRU_PHY_PROFILE: This 3-bit field indicates the PHY profile type of the(i+1)^(th) (i is the loop index) frame of the associated FRU. This fielduses the same signaling format as shown in the table 8.

FRU_FRAME_LENGTH: This 2-bit field indicates the length of the(i+1)^(th) frame of the associated FRU. Using FRU_FRAME_LENGTH togetherwith FRU_GI_FRACTION, the exact value of the frame duration can beobtained.

FRU_GI_FRACTION: This 3-bit field indicates the guard interval fractionvalue of the (i+1)^(th) frame of the associated FRU. FRU_GI_FRACTION issignaled according to the table 7.

RESERVED: This 4-bit field is reserved for future use.

The following fields provide parameters for decoding the PLS2 data.

PLS2_FEC_TYPE: This 2-bit field indicates the FEC type used by the PLS2protection. The FEC type is signaled according to table 10. The detailsof the LDPC codes will be described later.

TABLE 10 Content PLS2 FEC type 00 4K-1/4 and 7K-3/10 LDPC codes 01~11Reserved

PLS2_MOD: This 3-bit field indicates the modulation type used by thePLS2. The modulation type is signaled according to table 11.

TABLE 11 Value PLS2_MODE 000 BPSK 001 QPSK 010 QAM-16 011 NUQ-64 100~111Reserved

PLS2_SIZE_CELL: This 15-bit field indicates C_(total) _(_) _(parbal)_(_) _(block), the size (specified as the number of QAM cells) of thecollection of full coded blocks for PLS2 that is carried in the currentframe-group. This value is constant during the entire duration of thecurrent frame-group.

PLS2_STAT_SIZE_BIT: This 14-bit field indicates the size, in bits, ofthe PLS2-STAT for the current frame-group. This value is constant duringthe entire duration of the current frame-group.

PLS2_DYN_SIZE_BIT: This 14-bit field indicates the size, in bits, of thePLS2-DYN for the current frame-group. This value is constant during theentire duration of the current frame-group.

PLS2_REP_FLAG: This 1-bit flag indicates whether the PLS2 repetitionmode is used in the current frame-group. When this field is set to value‘1’, the PLS2 repetition mode is activated. When this field is set tovalue ‘0’, the PLS2 repetition mode is deactivated.

PLS2_REP_SIZE_CELL: This 15-bit field indicates C_(total) _(_) _(parbal)_(_) _(block), the size (specified as the number of QAM cells) of thecollection of partial coded blocks for PLS2 carried in every frame ofthe current frame-group, when PLS2 repetition is used. If repetition isnot used, the value of this field is equal to 0. This value is constantduring the entire duration of the current frame-group.

PLS2_NEXT_FEC_TYPE: This 2-bit field indicates the FEC type used forPLS2 that is carried in every frame of the next frame-group. The FECtype is signaled according to the table 10.

PLS2_NEXT_MOD: This 3-bit field indicates the modulation type used forPLS2 that is carried in every frame of the next frame-group. Themodulation type is signaled according to the table 11.

PLS2_NEXT_REP_FLAG: This 1-bit flag indicates whether the PLS2repetition mode is used in the next frame-group. When this field is setto value ‘1’, the PLS2 repetition mode is activated. When this field isset to value ‘0’, the PLS2 repetition mode is deactivated.

PLS2_NEXT_REP_SIZE_CELL: This 15-bit field indicates C_(total) _(_)_(full) _(_) _(block), The size (specified as the number of QAM cells)of the collection of full coded blocks for PLS2 that is carried in everyframe of the next frame-group, when PLS2 repetition is used. Ifrepetition is not used in the next frame-group, the value of this fieldis equal to 0. This value is constant during the entire duration of thecurrent frame-group.

PLS2_NEXT_REP_STAT_SIZE_BIT: This 14-bit field indicates the size, inbits, of the PLS2-STAT for the next frame-group. This value is constantin the current frame-group.

PLS2_NEXT_REP_DYN_SIZE_BIT: This 14-bit field indicates the size, inbits, of the PLS2-DYN for the next frame-group. This value is constantin the current frame-group.

PLS2_AP_MODE: This 2-bit field indicates whether additional parity isprovided for PLS2 in the current frame-group. This value is constantduring the entire duration of the current frame-group. The below table12 gives the values of this field. When this field is set to ‘00’,additional parity is not used for the PLS2 in the current frame-group.

TABLE 12 Value PLS2-AP mode 00 AP is not provided 01 AP1 mode 10~11Reserved

PLS2_AP_SIZE_CELL: This 15-bit field indicates the size (specified asthe number of QAM cells) of the additional parity bits of the PLS2. Thisvalue is constant during the entire duration of the current frame-group.

PLS2_NEXT_AP_MODE: This 2-bit field indicates whether additional parityis provided for PLS2 signaling in every frame of next frame-group. Thisvalue is constant during the entire duration of the current frame-group.The table 12 defines the values of this field

PLS2_NEXT_AP_SIZE_CELL: This 15-bit field indicates the size (specifiedas the number of QAM cells) of the additional parity bits of the PLS2 inevery frame of the next frame-group. This value is constant during theentire duration of the current frame-group.

RESERVED: This 32-bit field is reserved for future use.

CRC_32: A 32-bit error detection code, which is applied to the entirePLS1 signaling.

FIG. 14 illustrates PLS2 data according to an embodiment of the presentinvention.

FIG. 14 illustrates PLS2-STAT data of the PLS2 data. The PLS2-STAT dataare the same within a frame-group, while the PLS2-DYN data provideinformation that is specific for the current frame.

The details of fields of the PLS2-STAT data are as follows:

FIC_FLAG: This 1-bit field indicates whether the FIC is used in thecurrent frame-group. If this field is set to ‘1’, the FIC is provided inthe current frame. If this field set to ‘0’, the FIC is not carried inthe current frame. This value is constant during the entire duration ofthe current frame-group.

AUX_FLAG: This 1-bit field indicates whether the auxiliary stream(s) isused in the current frame-group. If this field is set to ‘1’, theauxiliary stream is provided in the current frame. If this field set to‘0’, the auxiliary stream is not carried in the current frame. Thisvalue is constant during the entire duration of current frame-group.

NUM_DP: This 6-bit field indicates the number of DPs carried within thecurrent frame. The value of this field ranges from 1 to 64, and thenumber of DPs is NUM_DP+1.

DP_ID: This 6-bit field identifies uniquely a DP within a PHY profile.

DP_TYPE: This 3-bit field indicates the type of the DP. This is signaledaccording to the below table 13.

TABLE 13 Value DP Type 000 DP Type 1 001 DP Type 2 010~111 reserved

DP_GROUP_ID: This 8-bit field identifies the DP group with which thecurrent DP is associated. This can be used by a receiver to access theDPs of the service components associated with a particular service,which will have the same DP_GROUP_ID.

BASE_DP_ID: This 6-bit field indicates the DP carrying service signalingdata (such as PSI/SI) used in the Management layer. The DP indicated byBASE_DP_ID may be either a normal DP carrying the service signaling dataalong with the service data or a dedicated DP carrying only the servicesignaling data

DP_FEC_TYPE: This 2-bit field indicates the FEC type used by theassociated DP. The FEC type is signaled according to the below table 14.

TABLE 14 Value FEC_TYPE 00 16K LDPC 01 64K LDPC 10~11 Reserved

DP_COD: This 4-bit field indicates the code rate used by the associatedDP. The code rate is signaled according to the below table 15.

TABLE 15 Value Code rate 0000 5/15 0001 6/15 0010 7/15 0011 8/15 01009/15 0101 10/15 0110 11/15 0111 12/15 1000 13/15 1001~1111 Reserved

DP_MOD: This 4-bit field indicates the modulation used by the associatedDP. The modulation is signaled according to the below table 16.

TABLE 16 Value Modulation 0000 QPSK 0001 QAM-16 0010 NUQ-64 0011 NUQ-2560100 NUQ-1024 0101 NUC-16 0110 NUC-64 0111 NUC-256 1000 NUC-10241001~1111 reserved

DP_SSD_FLAG: This 1-bit field indicates whether the SSD mode is used inthe associated DP. If this field is set to value ‘1’, SSD is used. Ifthis field is set to value ‘0’, SSD is not used.

The following field appears only if PHY_PROFILE is equal to ‘010’, whichindicates the advanced profile:

DP_MIMO: This 3-bit field indicates which type of MIMO encoding processis applied to the associated DP. The type of MIMO encoding process issignaled according to the table 17.

TABLE 17 Value MIMO encoding 000 FR-SM 001 FRFD-SM 010~111 reserved

DP_TI_TYPE: This 1-bit field indicates the type of time-interleaving. Avalue of ‘0’ indicates that one TI group corresponds to one frame andcontains one or more TI-blocks. A value of ‘1’ indicates that one TIgroup is carried in more than one frame and contains only one TI-block.

DP_TI_LENGTH: The use of this 2-bit field (the allowed values are only1, 2, 4, 8) is determined by the values set within the DP_TI_TYPE fieldas follows:

If the DP_TI_TYPE is set to the value ‘1’, this field indicates P_(I),the number of the frames to which each TI group is mapped, and there isone TI-block per TI group (N_(TI)=1). The allowed P_(I) values with2-bit field are defined in the below table 18.

If the DP_TI_TYPE is set to the value ‘0’, this field indicates thenumber of TI-blocks N_(TI) per TI group, and there is one TI group perframe (P_(I)=1). The allowed P_(I) values with 2-bit field are definedin the below table 18.

TABLE 18 2-bit field P_(I) N_(TI) 00 1 1 01 2 2 10 4 3 11 8 4

DP_FRAME_INTERVAL: This 2-bit field indicates the frame interval(I_(JUMP)) within the frame-group for the associated DP and the allowedvalues are 1, 2, 4, 8 (the corresponding 2-bit field is ‘00’, ‘01’,‘10’, or ‘11’, respectively). For DPs that do not appear every frame ofthe frame-group, the value of this field is equal to the intervalbetween successive frames. For example, if a DP appears on the frames 1,5, 9, 13, etc., this field is set to ‘4’. For DPs that appear in everyframe, this field is set to ‘1’.

DP_TI_BYPASS: This 1-bit field determines the availability of timeinterleaver. If time interleaving is not used for a DP, it is set to‘1’. Whereas if time interleaving is used it is set to ‘0’.

DP_FIRST_FRAME_IDX: This 5-bit field indicates the index of the firstframe of the super-frame in which the current DP occurs. The value ofDP_FIRST_FRAME_IDX ranges from 0 to 31

DP_NUM_BLOCK_MAX: This 10-bit field indicates the maximum value ofDP_NUM_BLOCKS for this DP. The value of this field has the same range asDP_NUM_BLOCKS.

DP_PAYLOAD_TYPE: This 2-bit field indicates the type of the payload datacarried by the given DP. DP_PAYLOAD_TYPE is signaled according to thebelow table 19.

TABLE 19 Value Payload Type 00 TS. 01 IP 10 GS 11 reserved

DP_INBAND_MODE: This 2-bit field indicates whether the current DPcarries in-band signaling information. The in-band signaling type issignaled according to the below table 20.

TABLE 20 Value In-band mode 00 In-band signaling is not carried. 01INBAND-PLS is carried only 10 INBAND-ISSY is carried only 11 INBAND-PLSand INBAND-ISSY are carried

DP_PROTOCOL_TYPE: This 2-bit field indicates the protocol type of thepayload carried by the given DP. It is signaled according to the belowtable 21 when input payload types are selected.

TABLE 21 If If If DP_PAYLOAD_ DP_PAYLOAD_ DP_PAYLOAD_ TYPE TYPE TYPEValue Is TS Is IP Is GS 00 MPEG2-TS IPv4 (Note) 01 Reserved IPv6Reserved 10 Reserved Reserved Reserved 11 Reserved Reserved Reserved

DP_CRC_MODE: This 2-bit field indicates whether CRC encoding is used inthe Input Formatting block. The CRC mode is signaled according to thebelow table 22.

TABLE 22 Value CRC mode 00 Not used 01 CRC-8 10 CRC-16 11 CRC-32

DNP_MODE: This 2-bit field indicates the null-packet deletion mode usedby the associated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). DNP_MODEis signaled according to the below table 23. If DP_PAYLOAD_TYPE is notTS (‘00’), DNP_MODE is set to the value ‘00’.

TABLE 23 Value Null-packet deletion mode 00 Not used 01 DNP-NORMAL 10DNP-OFFSET 11 reserved

ISSY_MODE: This 2-bit field indicates the ISSY mode used by theassociated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). The ISSY_MODE issignaled according to the below table 24 If DP_PAYLOAD_TYPE is not TS(‘00’), ISSY_MODE is set to the value ‘00’.

TABLE 24 Value ISSY mode 00 Not used 01 ISSY-UP 10 ISSY-BBF 11 reserved

HC_MODE_TS: This 2-bit field indicates the TS header compression modeused by the associated DP when DP_PAYLOAD_TYPE is set to TS (‘00’). TheHC_MODE_TS is signaled according to the below table 25.

TABLE 25 Value Header compression mode 00 HC_MODE_TS 1 01 HC_MODE_TS 210 HC_MODE_TS 3 11 HC_MODE_TS 4

HC_MODE_IP: This 2-bit field indicates the IP header compression modewhen DP_PAYLOAD_TYPE is set to IP (‘01’). The HC_MODE_IP is signaledaccording to the below table 26.

TABLE 26 Value Header compression mode 00 No compression 01 HC_MODE_IP 110~11 reserved

PID: This 13-bit field indicates the PID number for TS headercompression when DP_PAYLOAD_TYPE is set to TS (‘00’) and HC_MODE_TS isset to ‘01’ or ‘10’.

RESERVED: This 8-bit field is reserved for future use.

The following field appears only if FIC_FLAG is equal to ‘1’:

FIC_VERSION: This 8-bit field indicates the version number of the FIC.

FIC_LENGTH_BYTE: This 13-bit field indicates the length, in bytes, ofthe FIC.

RESERVED: This 8-bit field is reserved for future use.

The following field appears only if AUX_FLAG is equal to ‘1’:

NUM_AUX: This 4-bit field indicates the number of auxiliary streams.Zero means no auxiliary streams are used.

AUX_CONFIG_RFU: This 8-bit field is reserved for future use.

AUX_STREAM_TYPE: This 4-bit is reserved for future use for indicatingthe type of the current auxiliary stream.

AUX_PRIVATE_CONFIG: This 28-bit field is reserved for future use forsignaling auxiliary streams.

FIG. 15 illustrates PLS2 data according to another embodiment of thepresent invention.

FIG. 15 illustrates PLS2-DYN data of the PLS2 data. The values of thePLS2-DYN data may change during the duration of one frame-group, whilethe size of fields remains constant.

The details of fields of the PLS2-DYN data are as follows:

FRAME_INDEX: This 5-bit field indicates the frame index of the currentframe within the super-frame. The index of the first frame of thesuper-frame is set to ‘0’.

PLS_CHANGE_COUNTER: This 4-bit field indicates the number ofsuper-frames ahead where the configuration will change. The nextsuper-frame with changes in the configuration is indicated by the valuesignaled within this field. If this field is set to the value ‘0000’, itmeans that no scheduled change is foreseen: e.g., value ‘1’ indicatesthat there is a change in the next super-frame.

FIC_CHANGE_COUNTER: This 4-bit field indicates the number ofsuper-frames ahead where the configuration (i.e., the contents of theFIC) will change. The next super-frame with changes in the configurationis indicated by the value signaled within this field. If this field isset to the value ‘0000’, it means that no scheduled change is foreseen:e.g. value ‘0001’ indicates that there is a change in the nextsuper-frame.

RESERVED: This 16-bit field is reserved for future use.

The following fields appear in the loop over NUM_DP, which describe theparameters associated with the DP carried in the current frame.

DP_ID: This 6-bit field indicates uniquely the DP within a PHY profile.

DP_START: This 15-bit (or 13-bit) field indicates the start position ofthe first of the DPs using the DPU addressing scheme. The DP_START fieldhas differing length according to the PHY profile and FFT size as shownin the below table 27.

TABLE 27 PHY DP_START field size profile 64K 16K Base 13 bit 15 bitHandheld — 13 bit Advanced 13 bit 15 bit

DP_NUM_BLOCK: This 10-bit field indicates the number of FEC blocks inthe current TI group for the current DP. The value of DP_NUM_BLOCKranges from 0 to 1023

RESERVED: This 8-bit field is reserved for future use.

The following fields indicate the FIC parameters associated with theEAC.

EAC_FLAG: This 1-bit field indicates the existence of the EAC in thecurrent frame. This bit is the same value as the EAC_FLAG in thepreamble.

EAS_WAKE_UP_VERSION_NUM: This 8-bit field indicates the version numberof a wake-up indication.

If the EAC_FLAG field is equal to ‘1’, the following 12 bits areallocated for EAC_LENGTH_BYTE field. If the EAC_FLAG field is equal to‘0’, the following 12 bits are allocated for EAC_COUNTER.

EAC_LENGTH_BYTE: This 12-bit field indicates the length, in byte, of theEAC.

EAC_COUNTER: This 12-bit field indicates the number of the frames beforethe frame where the EAC arrives.

The following field appears only if the AUX_FLAG field is equal to ‘1’:

AUX_PRIVATE_DYN: This 48-bit field is reserved for future use forsignaling auxiliary streams. The meaning of this field depends on thevalue of AUX_STREAM_TYPE in the configurable PLS2-STAT.

CRC_32: A 32-bit error detection code, which is applied to the entirePLS2.

FIG. 16 illustrates a logical structure of a frame according to anembodiment of the present invention.

As above mentioned, the PLS, EAC, FIC, DPs, auxiliary streams and dummycells are mapped into the active carriers of the OFDM symbols in theframe. The PLS1 and PLS2 are first mapped into one or more FSS(s). Afterthat, EAC cells, if any, are mapped immediately following the PLS field,followed next by FIC cells, if any. The DPs are mapped next after thePLS or EAC, FIC, if any. Type 1 DPs follows first, and Type 2 DPs next.The details of a type of the DP will be described later. In some case,DPs may carry some special data for EAS or service signaling data. Theauxiliary stream or streams, if any, follow the DPs, which in turn arefollowed by dummy cells. Mapping them all together in the abovementioned order, i.e. PLS, EAC, FIC, DPs, auxiliary streams and dummydata cells exactly fill the cell capacity in the frame.

FIG. 17 illustrates PLS mapping according to an embodiment of thepresent invention.

PLS cells are mapped to the active carriers of FSS(s). Depending on thenumber of cells occupied by PLS, one or more symbols are designated asFSS(s), and the number of FSS(s) N_(FSS) is signaled by NUM_FSS in PLS1.The FSS is a special symbol for carrying PLS cells. Since robustness andlatency are critical issues in the PLS, the FSS(s) has higher density ofpilots allowing fast synchronization and frequency-only interpolationwithin the FSS.

PLS cells are mapped to active carriers of the N_(FSS) FSS(s) in atop-down manner as shown in an example in FIG. 17. The PLS1 cells aremapped first from the first cell of the first FSS in an increasing orderof the cell index. The PLS2 cells follow immediately after the last cellof the PLS1 and mapping continues downward until the last cell index ofthe first FSS. If the total number of required PLS cells exceeds thenumber of active carriers of one FSS, mapping proceeds to the next FSSand continues in exactly the same manner as the first FSS.

After PLS mapping is completed, DPs are carried next. If EAC, FIC orboth are present in the current frame, they are placed between PLS and“normal” DPs.

FIG. 18 illustrates EAC mapping according to an embodiment of thepresent invention.

EAC is a dedicated channel for carrying EAS messages and links to theDPs for EAS. EAS support is provided but EAC itself may or may not bepresent in every frame. EAC, if any, is mapped immediately after thePLS2 cells. EAC is not preceded by any of the FIC, DPs, auxiliarystreams or dummy cells other than the PLS cells. The procedure ofmapping the EAC cells is exactly the same as that of the PLS.

The EAC cells are mapped from the next cell of the PLS2 in increasingorder of the cell index as shown in the example in FIG. 18. Depending onthe EAS message size, EAC cells may occupy a few symbols, as shown inFIG. 18.

EAC cells follow immediately after the last cell of the PLS2, andmapping continues downward until the last cell index of the last FSS. Ifthe total number of required EAC cells exceeds the number of remainingactive carriers of the last FSS mapping proceeds to the next symbol andcontinues in exactly the same manner as FSS(s). The next symbol formapping in this case is the normal data symbol, which has more activecarriers than a FSS.

After EAC mapping is completed, the FIC is carried next, if any exists.If FIC is not transmitted (as signaled in the PLS2 field), DPs followimmediately after the last cell of the EAC.

FIG. 19 illustrates FIC mapping according to an embodiment of thepresent invention.

(a) shows an example mapping of FIC cell without EAC and (b) shows anexample mapping of FIC cell with EAC.

FIC is a dedicated channel for carrying cross-layer information toenable fast service acquisition and channel scanning. This informationprimarily includes channel binding information between DPs and theservices of each broadcaster. For fast scan, a receiver can decode FICand obtain information such as broadcaster ID, number of services, andBASE_DP_ID. For fast service acquisition, in addition to FIC, base DPcan be decoded using BASE_DP_ID. Other than the content it carries, abase DP is encoded and mapped to a frame in exactly the same way as anormal DP. Therefore, no additional description is required for a baseDP. The FIC data is generated and consumed in the Management Layer. Thecontent of FIC data is as described in the Management Layerspecification.

The FIC data is optional and the use of FIC is signaled by the FIC_FLAGparameter in the static part of the PLS2. If FIC is used, FIC_FLAG isset to ‘1’ and the signaling field for FIC is defined in the static partof PLS2. Signaled in this field are FIC_VERSION, and FIC_LENGTH_BYTE.FIC uses the same modulation, coding and time interleaving parameters asPLS2. FIC shares the same signaling parameters such as PLS2_MOD andPLS2_FEC. FIC data, if any, is mapped immediately after PLS2 or EAC ifany. FIC is not preceded by any normal DPs, auxiliary streams or dummycells. The method of mapping FIC cells is exactly the same as that ofEAC which is again the same as PLS.

Without EAC after PLS, FIC cells are mapped from the next cell of thePLS2 in an increasing order of the cell index as shown in an example in(a). Depending on the FIC data size, FIC cells may be mapped over a fewsymbols, as shown in (b).

FIC cells follow immediately after the last cell of the PLS2, andmapping continues downward until the last cell index of the last FSS. Ifthe total number of required FIC cells exceeds the number of remainingactive carriers of the last FSS, mapping proceeds to the next symbol andcontinues in exactly the same manner as FSS(s). The next symbol formapping in this case is the normal data symbol which has more activecarriers than a FSS.

If EAS messages are transmitted in the current frame, EAC precedes FIC,and FIC cells are mapped from the next cell of the EAC in an increasingorder of the cell index as shown in (b).

After FIC mapping is completed, one or more DPs are mapped, followed byauxiliary streams, if any, and dummy cells.

FIG. 20 illustrates a type of DP according to an embodiment of thepresent invention.

(a) shows type 1 DP and (b) shows type 2 DP.

After the preceding channels, i.e., PLS, EAC and FIC, are mapped, cellsof the DPs are mapped. A DP is categorized into one of two typesaccording to mapping method:

Type 1 DP: DP is mapped by TDM

Type 2 DP: DP is mapped by FDM

The type of DP is indicated by DP_TYPE field in the static part of PLS2.FIG. 20 illustrates the mapping orders of Type 1 DPs and Type 2 DPs.Type 1 DPs are first mapped in the increasing order of cell index, andthen after reaching the last cell index, the symbol index is increasedby one. Within the next symbol, the DP continues to be mapped in theincreasing order of cell index starting from p=0. With a number of DPsmapped together in one frame, each of the Type 1 DPs are grouped intime, similar to TDM multiplexing of DPs.

Type 2 DPs are first mapped in the increasing order of symbol index, andthen after reaching the last OFDM symbol of the frame, the cell indexincreases by one and the symbol index rolls back to the first availablesymbol and then increases from that symbol index. After mapping a numberof DPs together in one frame, each of the Type 2 DPs are grouped infrequency together, similar to FDM multiplexing of DPs.

Type 1 DPs and Type 2 DPs can coexist in a frame if needed with onerestriction; Type 1 DPs always precede Type 2 DPs. The total number ofOFDM cells carrying Type 1 and Type 2 DPs cannot exceed the total numberof OFDM cells available for transmission of DPs:D _(DP1) +D _(DP2) ≦D _(DP)  [Math FIG. 2]

where D_(DP1) is the number of OFDM cells occupied by Type 1 DPs,D_(DP2) is the number of cells occupied by Type 2 DPs. Since PLS, EAC,FIC are all mapped in the same way as Type 1 DP, they all follow “Type 1mapping rule”. Hence, overall, Type 1 mapping always precedes Type 2mapping.

FIG. 21 illustrates DP mapping according to an embodiment of the presentinvention.

(a) shows an addressing of OFDM cells for mapping type 1 DPs and (b)shows an an addressing of OFDM cells for mapping for type 2 DPs.

Addressing of OFDM cells for mapping Type 1 DPs (0, . . . , D_(DP1)−1)is defined for the active data cells of Type 1 DPs. The addressingscheme defines the order in which the cells from the TIs for each of theType 1 DPs are allocated to the active data cells. It is also used tosignal the locations of the DPs in the dynamic part of the PLS2.

Without EAC and FIC, address 0 refers to the cell immediately followingthe last cell carrying PLS in the last FSS. If EAC is transmitted andFIC is not in the corresponding frame, address 0 refers to the cellimmediately following the last cell carrying EAC. If FIC is transmittedin the corresponding frame, address 0 refers to the cell immediatelyfollowing the last cell carrying FIC. Address 0 for Type 1 DPs can becalculated considering two different cases as shown in (a). In theexample in (a), PLS, EAC and FIC are assumed to be all transmitted.Extension to the cases where either or both of EAC and FIC are omittedis straightforward. If there are remaining cells in the FSS aftermapping all the cells up to FIC as shown on the left side of (a).

Addressing of OFDM cells for mapping Type 2 DPs (0, . . . , D_(DP2)−1)is defined for the active data cells of Type 2 DPs. The addressingscheme defines the order in which the cells from the TIs for each of theType 2 DPs are allocated to the active data cells. It is also used tosignal the locations of the DPs in the dynamic part of the PLS2.

Three slightly different cases are possible as shown in (b). For thefirst case shown on the left side of (b), cells in the last FSS areavailable for Type 2 DP mapping. For the second case shown in themiddle, FIC occupies cells of a normal symbol, but the number of FICcells on that symbol is not larger than C_(FSS). The third case, shownon the right side in (b), is the same as the second case except that thenumber of FIC cells mapped on that symbol exceeds C_(FSS).

The extension to the case where Type 1 DP(s) precede Type 2 DP(s) isstraightforward since PLS, EAC and FIC follow the same “Type 1 mappingrule” as the Type 1 DP(s).

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention.

FIG. 22 illustrates an FEC structure according to an embodiment of thepresent invention before bit interleaving. As above mentioned, Data FECencoder may perform the FEC encoding on the input BBF to generateFECBLOCK procedure using outer coding (BCH), and inner coding (LDPC).The illustrated FEC structure corresponds to the FECBLOCK. Also, theFECBLOCK and the FEC structure have same value corresponding to a lengthof LDPC codeword.

The BCH encoding is applied to each BBF (K_(bch) bits), and then LDPCencoding is applied to BCH-encoded BBF (K_(ldpc) bits=N_(bch) bits) asillustrated in FIG. 22.

The value of N_(ldpc) is either 64800 bits (long FECBLOCK) or 16200 bits(short FECBLOCK).

The below table 28 and table 29 show FEC encoding parameters for a longFECBLOCK and a short FECBLOCK, respectively.

TABLE 28 BCH error LDPC correction N_(bch)- Rate N_(ldpc) K_(ldpc)K_(bch) capability K_(bch) 5/15 64800 21600 21408 12 192 6/15 2592025728 7/15 30240 30048 8/15 34560 34368 9/15 38880 38688 10/15  4320043008 11/15  47520 47328 12/15  51840 51648 13/15  56160 55968

TABLE 29 BCH error LDPC correction N_(bch)- Rate N_(ldpc) K_(ldpc)K_(bch) capability K_(bch) 5/15 16200 5400 5232 12 168 6/15 6480 63127/15 7560 7392 8/15 8640 8472 9/15 9720 9552 10/15  10800 10632 11/15 11880 11712 12/15  12960 12792 13/15  14040 13872

The details of operations of the BCH encoding and LDPC encoding are asfollows:

A 12-error correcting BCH code is used for outer encoding of the BBF.The BCH generator polynomial for short FECBLOCK and long FECBLOCK areobtained by multiplying together all polynomials.

LDPC code is used to encode the output of the outer BCH encoding. Togenerate a completed B_(ldpc) (FECBLOCK), P_(ldpc) (parity bits) isencoded systematically from each I_(ldpc) (BCH-encoded BBF), andappended to I_(ldpc). The completed B_(ldpc) (FECBLOCK) are expressed asfollow Math figure.B _(ldpc) =[I _(ldpc) P _(ldpc) ]=[i ₀ ,i ₁ , . . . ,i _(K) _(ldpc) −1,p₀ ,p ₁ , . . . ,p _(N) _(ldpc) _(-K) _(ldpc) ₋₁]  [Math FIG. 3]

The parameters for long FECBLOCK and short FECBLOCK are given in theabove table 28 and 29, respectively.

The detailed procedure to calculate N_(ldpc)-K_(ldpc) parity bits forlong FECBLOCK, is as follows:

1) Initialize the parity bits,p ₀ =p ₁ =p ₂ = . . . =p _(N) _(ldpc) _(-K) _(ldpc) ₋₁=0  [Math FIG. 4]

2) Accumulate the first information bit—i₀, at parity bit addressesspecified in the first row of an addresses of parity check matrix. Thedetails of addresses of parity check matrix will be described later. Forexample, for rate 13/15:p ₉₈₃ =p ₉₈₃ ⊕i ₀ p ₂₈₁₅ =p ₂₈₁₅ ⊕i ₀p ₄₈₃₇ =p ₄₈₃₇ ⊕i ₀ p ₄₉₈₉ =p ₄₉₈₉ ⊕i ₀p ₆₁₃₈ =p ₆₁₃₃ ⊕i ₀ p ₆₄₅₈ =p ₆₄₅₃ ⊕i ₀p ₆₉₂₁ =p ₆₉₂₁ ⊕i ₀ p ₆₉₇₄ =p ₆₉₇₄ ⊕i ₀p ₇₅₇₂ =p ₇₅₇₂ ⊕i ₀ p ₈₂₆₀ =p ₈₂₆₀ ⊕i ₀p ₈₄₉₆ =p ₈₄₉₆ ⊕i ₀  [Math FIGS. 5]

3) For the next 359 information bits, i_(s), s=1, 2, . . . , 359accumulate i_(s) at parity bit addresses using following Math figure.{x+(s mod 360)×Q _(ldpc)} mod(N _(ldpc) −K _(ldpc))  [Math FIG. 6]

where x denotes the address of the parity bit accumulator correspondingto the first bit i₀, and Q_(ldpc) is a code rate dependent constantspecified in the addresses of parity check matrix. Continuing with theexample, Q_(ldpc)=24 for rate 13/15, so for information bit i₁, thefollowing operations are performed:p ₁₀₀₇ =p⊕i ₁ p ₇₈₃₉ =p ₇₈₃₉ ⊕i ₁p ₄₈₆₁ =p ₄₈₆₁ ⊕i ₁ p ₅₀₁₃ =p ₅₀₁₃ ⊕i ₁p ₆₁₆₂ =p ₆₁₆₂ ⊕i ₁ p ₆₄₈₇ =p ₆₄₈₂ ⊕i ₁p ₆₉₄₅ =p ₆₉₄₅ ⊕i ₁ p ₆₉₉₈ =p ₆₉₉₈ ⊕i ₁p ₇₅₉₆ =p ₇₅₉₆ ⊕i ₁ P ₈₂₈₄ =P ₈₂₈₄ ⊕i ₁p ₈₅₂₀ =p ₈₅₂₀ ⊕i ₁  [Math FIG. 7]

4) For the 361st information bit i₃₆₀, the addresses of the parity bitaccumulators are given in the second row of the addresses of paritycheck matrix. In a similar manner the addresses of the parity bitaccumulators for the following 359 information bits i_(s), s=361, 362, .. . , 719 are obtained using the Math FIG. 6, where x denotes theaddress of the parity bit accumulator corresponding to the informationbit i₃₆₀, i.e., the entries in the second row of the addresses of paritycheck matrix.

5) In a similar manner, for every group of 360 new information bits, anew row from addresses of parity check matrixes used to find theaddresses of the parity bit accumulators.

After all of the information bits are exhausted, the final parity bitsare obtained as follows:

6) Sequentially perform the following operations starting with i=1p _(i) =p _(i) ⊕p _(i-1) , i=1,2, . . . ,N _(ldpc) −K _(ldpc)−1  [MathFIG. 8]

where final content of p_(i), i=0, 1, . . . , N_(ldpc)−K_(ldpc)−1 isequal to the parity bit p_(i).

[Table 30]

TABLE 30 Code Rate Q_(ldpc) 5/15 120 6/15 108 7/15 96 8/15 84 9/15 7210/15  60 11/15  48 12/15  36 13/15  24

This LDPC encoding procedure for a short FECBLOCK is in accordance witht LDPC encoding procedure for the long FECBLOCK, except replacing thetable 30 with table 31, and replacing the addresses of parity checkmatrix for the long FECBLOCK with the addresses of parity check matrixfor the short FECBLOCK.

TABLE 31 Code Rate Q_(ldpc) 5/15 30 6/15 27 7/15 24 8/15 21 9/15 1810/15  15 11/15  12 12/15  9 13/15  6

FIG. 23 illustrates a bit interleaving according to an embodiment of thepresent invention.

The outputs of the LDPC encoder are bit-interleaved, which consists ofparity interleaving followed by Quasi-Cyclic Block (QCB) interleavingand inner-group interleaving.

(a) shows Quasi-Cyclic Block (QCB) interleaving and (b) showsinner-group interleaving.

The FECBLOCK may be parity interleaved. At the output of the parityinterleaving, the LDPC codeword consists of 180 adjacent QC blocks in along FECBLOCK and 45 adjacent QC blocks in a short FECBLOCK. Each QCblock in either a long or short FECBLOCK consists of 360 bits. Theparity interleaved LDPC codeword is interleaved by QCB interleaving. Theunit of QCB interleaving is a QC block. The QC blocks at the output ofparity interleaving are permutated by QCB interleaving as illustrated inFIG. 23, where N_(cells)=64800/η_(mod) or 16200/η_(mod) according to theFECBLOCK length. The QCB interleaving pattern is unique to eachcombination of modulation type and LDPC code rate.

After QCB interleaving, inner-group interleaving is performed accordingto modulation type and order (η_(mod)) which is defined in the belowtable 32. The number of QC blocks for one inner-group, N_(QCB) _(_)_(IG), is also defined.

TABLE 32 Modulation type η_(mod) N_(QCB)_IG QAM-16 4 2 NUC-16 4 4 NUQ-646 3 NUC-64 6 6 NUQ-256 8 4 NUC-256 8 8 NUQ-1024 10 5 NUC-1024 10 10

The inner-group interleaving process is performed with N_(QGB) _(_)_(IG) QC blocks of the QCB interleaving output. Inner-group interleavinghas a process of writing and reading the bits of the inner-group using360 columns and N_(QGB) _(_) _(IG) rows. In the write operation, thebits from the QCB interleaving output are written row-wise. The readoperation is performed column-wise to read out m bits from each row,where m is equal to 1 for NUC and 2 for NUQ.

FIG. 24 illustrates a cell-word demultiplexing according to anembodiment of the present invention.

(a) shows a cell-word demultiplexing for 8 and 12 bpcu MIMO and (b)shows a cell-word demultiplexing for 10 bpcu MIMO.

Each cell word (c_(0,l), c_(1,l), . . . , c_(η mod-1,l)) of the bitinterleaving output is demultiplexed into (d_(1,0,m), d_(1,1,m) . . . ,d_(1,η mod-1,m)) and (d_(2,0,m), d_(2,1,m) . . . , d_(2,η mod-1,m)) asshown in (a), which describes the cell-word demultiplexing process forone XFECBLOCK.

For the 10 bpcu MIMO case using different types of NUQ for MIMOencoding, the Bit Interleaver for NUQ-1024 is re-used. Each cell word(c_(0,l), c_(1,l), . . . , c_(9,l)) of the Bit Interleaver output isdemultiplexed into (d_(1,0,m), d_(1,l,m), . . . , d_(1,3,m)) and(d_(2,0,m), d_(2,1,m), . . . , d_(2,5,m)), as shown in (b).

FIG. 25 illustrates a time interleaving according to an embodiment ofthe present invention.

(a) to (c) show examples of TI mode.

The time interleaver operates at the DP level. The parameters of timeinterleaving (TI) may be set differently for each DP.

The following parameters, which appear in part of the PLS2-STAT data,configure the TI:

DP_TI_TYPE (allowed values: 0 or 1): Represents the TI mode; ‘0’indicates the mode with multiple TI blocks (more than one TI block) perTI group. In this case, one TI group is directly mapped to one frame (nointer-frame interleaving). ‘1’ indicates the mode with only one TI blockper TI group. In this case, the TI block may be spread over more thanone frame (inter-frame interleaving).

DP_TI_LENGTH: If DP_TI_TYPE=‘0’, this parameter is the number of TIblocks N_(TT) per TI group. For DP_TI_TYPE=‘1’, this parameter is thenumber of frames P_(I) spread from one TI group.

DP_NUM_BLOCK_MAX (allowed values: 0 to 1023): Represents the maximumnumber of XFECBLOCKs per TI group.

DP_FRAME_INTERVAL (allowed values: 1, 2, 4, 8): Represents the number ofthe frames I_(JUMP) between two successive frames carrying the same DPof a given PHY profile.

DP_TI_BYPASS (allowed values: 0 or 1): If time interleaving is not usedfor a DP, this parameter is set to ‘1’. It is set to ‘0’ if timeinterleaving is used.

Additionally, the parameter DP_NUM_BLOCK from the PLS2-DYN data is usedto represent the number of XFECBLOCKs carried by one TI group of the DP.

When time interleaving is not used for a DP, the following TI group,time interleaving operation, and TI mode are not considered. However,the Delay Compensation block for the dynamic configuration informationfrom the scheduler will still be required. In each DP, the XFECBLOCKsreceived from the SSD/MIMO encoding are grouped into TI groups. That is,each TI group is a set of an integer number of XFECBLOCKs and willcontain a dynamically variable number of XFECBLOCKs. The number ofXFECBLOCKs in the TI group of index n is denoted by N_(xBLOCK) _(_)_(Group)(n) and is signaled as DP_NUM_BLOCK in the PLS2-DYN data. Notethat N_(xBLOCK) _(_) _(Group)(n) may vary from the minimum value of 0 tothe maximum value N_(xBLOCK) _(_) _(Group) _(_) _(MAX) (corresponding toDP_NUM_BLOCK_MAX) of which the largest value is 1023.

Each TI group is either mapped directly onto one frame or spread overP_(I) frames. Each TI group is also divided into more than one TI blocks(N_(TI)), where each TI block corresponds to one usage of timeinterleaver memory. The TI blocks within the TI group may containslightly different numbers of XFECBLOCKs. If the TI group is dividedinto multiple TI blocks, it is directly mapped to only one frame. Thereare three options for time interleaving (except the extra option ofskipping the time interleaving) as shown in the below table 33.

TABLE 33 Modes Descriptions Option-1 Each TI group contains one TI blockand is mapped directly to one frame as shown in (a). This option issignaled in the PLS2- STAT by DP_TI_TYPE = ‘0’ and DP_TI_LENGTH = ‘1’(N_(TI) = 1). Option-2 Each TI group contains one TI block and is mappedto more than one frame. (b) shows an example, where one TI group ismapped to two frames, i.e., DP_TI_LENGTH = ‘2’ (P₁ = 2) andDP_FRAME_INTERVAL (I_(JUMP) = 2). This provides greater time diversityfor low data-rate services. This option is signaled in the PLS2-STAT byDP_TI_TYPE = ‘1’. Option-3 Each TI group is divided into multiple TIblocks and is mapped directly to one frame as shown in (c). Each TIblock may use full TI memory, so as to provide the maximum bit-rate fora DP. This option is signaled in the PLS2-STAT signaling by DP_TI_TYPE =‘0’ and DP_TI_LENGTH = N_(TI), while P₁ = 1.

FIG. 26 illustrates a MIMO encoding block diagram according to anembodiment of the present invention.

The MIMO encoding scheme according to an embodiment of the presentinvention is optimized for broadcasting signal transmission. The MIMOtechnology is a promising way to get a capacity increase but it dependson channel characteristics. Especially for broadcasting, the strong LOScomponent of the channel or a difference in the received signal powerbetween two antennas caused by different signal propagationcharacteristics can make it difficult to get capacity gain from MIMO.The MIMO encoding scheme according to an embodiment of the presentinvention overcomes this problem using a rotation-based pre-coding andphase randomization of one of the MIMO output signals. MIMO encoding canbe intended for a 2×2 MIMO system requiring at least two antennas atboth the transmitter and the receiver.

MIMO processing can be required for the advanced profile frame, whichmeans all DPs in the advanced profile frame are processed by the MIMOencoder (or MIMO encoding module). MIMO processing can be applied at DPlevel. Pairs of the Constellation Mapper outputs NUQ (e_(1,i) ande_(2,i)) can be fed to the input of the MIMO Encoder. Paired MIMOEncoder output (g_(1,i) and g_(2,i)) can be transmitted by the samecarrier k and OFDM symbol 1 of their respective TX antennas.

The illustrated diagram shows the MIMO Encoding block, where i is theindex of the cell pair of the same XFECBLOCK and Ncells is the number ofcells per one XFECBLOCK.

FIG. 27 shows a MIMO encoding scheme according to one embodiment of thepresent invention.

If MIMO is used, a broadcast/communication system may transmit moredata. However, channel capacity of MIMO may be changed according tochannel environment. In addition, if Tx and Rx antennas are different interms of power or if correlation between channel is high, MIMOperformance may deteriorate.

If dual polar MIMO is used, two components may reach a receiver atdifferent power ratios according to propagation property ofvertical/horizontal polarity. That is, if dual polar MIMO is used, powerimbalance may occur between vertical and horizontal antennas. Here, dualpolar MIMO may mean MIMO using vertical/horizontal polarity of anantenna.

In addition, correlation between channel components may increase due toLOS environment between Tx and Rx antennas.

The present invention proposes a MIMO encoding/decoding technique forsolving problems occurring upon using MIMO, that is, a techniquesuitable for a correlated channel environment or a power imbalancedchannel environment. Here, the correlated channel environment may be anenvironment in which channel capacity is lowered and system operation isinterrupted if MIMO is used.

In particular, in a MIMO encoding scheme, a PH-eSM PI method and afull-rate full-diversity (FRFD) PH-eSM PI method are proposed inaddition to an existing PH-eSM method. The proposed methods may be MIMOencoding methods considering complexity of a receiver and a powerimbalanced channel environment. These two MIMO encoding schemes have norestriction on the antenna polarity configuration.

The PH-eSM PI method can provide capacity increase with relatively lowcomplexity increase at the receiver side. The PH-eSM PI method may bereferred to as a full-rate spatial multiplexing (FR-SM), FR-SM method, aFR-SM encoding process, etc. In the PH-eSM PI method, rotation angle isoptimized to overcome power imbalance with complexity of O (M2). In thePH-eSM PI method, it is possible to effectively cope with spatial powerimbalance between Tx antennas.

The FRFD PH-eSM PI method can provide capacity increase and additionaldiversity gain with a relatively great complexity increase at thereceiver side. The FRFD PH-eSM PI method may be referred to as afull-rate full-diversity spatial multiplexing (FRFD-SM), an FRFD-SMmethod, FRFD-SM encoding process, etc. In the FRFD PH-eSM PI method,additional Frequency diversity gain is achieved by adding complexity ofO (M4). In the FRFD PH-eSM PI method, unlike the PH-eSM PI method, it ispossible to effectively cope not only with power imbalance between Txantennas and but also with power imbalance between carriers.

In addition, the PH-eSM PI method and the FRFD PH-eSM PI method may beMIMO encoding schemes applied to symbols mapped to non-uniform QAM,respectively. Here, mapping to non-uniform QAM may mean thatconstellation mapping is performed using non-uniform QAM. Non-uniformQAM may be referred to as NU QAM, NUQ, etc. PH-eSM PI method and FRFDPH-eSM PI method can also be applied to symbols mapped onto either QAM(uniform QAM) or Non-uniform constellation. The MIMO encoding schemeapplied to symbols mapped to non-uniform QAM may have better BERperformance than the MIMO encoding scheme applied to symbols mapped toQAM (uniform QAM) per code rate in a power imbalanced situation.However, with certain code rate and bit per channel use, applying MIMOencoding to symbols mapped onto QAM performs better.

In addition, the PH-eSM method may also be applied to non-uniform QAM.Therefore, the present invention further proposes a PH-eSM methodapplied to symbols mapped to non-uniform QAM.

Hereinafter, constellation mapping will be described.

In constellation mapper, each cell word (c_(0,l), c_(1,l), . . . ,c_(η mod-1,l)) from the Bit Interleaver in the base and the handheldprofiles, or cell word (d_(i,0,l), d_(i,1,l), . . . , d_(i,η mod-1,l),where i=1, 2) from the Cell-word Demultiplexer in the advanced profilecan be modulated using either QPSK, QAM-16, non-uniform QAM (NUQ-64,NUQ-256, NUQ-1024) or non-uniform constellation (NUC-16, NUC-64,NUC-256, NUC-1024) to give a power-normalized constellation point,e_(l).

This constellation mapping is applied only for DPs. The constellationmapping for PLS1 and PLS2 can be different.

QAM-16 and NUQs are square shaped, while NUCs have arbitrary shape. Wheneach constellation is rotated by any multiple of 90 degrees, the rotatedconstellation overlaps with its original one. This ‘rotation-sense’symmetric property makes the capacities and the average powers of thereal and imaginary components equal to each other. Both NUQs and NUCsare defined specifically for each code rate and the particular one usedis signaled by the parameter DP_MOD in PLS2. The constellation shapesfor each code rate mapped onto the complex plane will be describedbelow. Hereinafter, the PH-eSM method and the PH-eSM PI method will bedescribed. A MIMO encoding equation used for the PH-eSM method and thePH-eSM PI method is expressed as follows.

$\begin{matrix}{\underset{X}{\begin{bmatrix}{X_{1}\left( f_{1} \right)} \\{X_{2}\left( f_{1} \right)}\end{bmatrix}} = {{\underset{\underset{P}{︸}}{{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & 0 \\0 & {\mathbb{e}}^{j\;{\phi{(q)}}}\end{bmatrix}}\begin{bmatrix}1 & a \\a & {- 1}\end{bmatrix}}\underset{S}{\begin{bmatrix}S_{1} \\S_{2}\end{bmatrix}}\mspace{14mu}{or}\mspace{14mu}\underset{X}{\begin{bmatrix}{X_{1}\left( f_{1} \right)} \\{X_{2}\left( f_{1} \right)}\end{bmatrix}}} = {\underset{\underset{P}{︸}}{{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & 0 \\0 & {\mathbb{e}}^{j\;{\phi{(q)}}}\end{bmatrix}}\begin{bmatrix}1 & {- a} \\a & 1\end{bmatrix}}\underset{S}{\begin{bmatrix}S_{1} \\S_{2}\end{bmatrix}}}}} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 9} \right\rbrack\end{matrix}$

That is, the above equation may be expressed as X=PS. Here, S₁ and S₂may denote a pair of input symbols. Here, P may denote a MIMO encodingmatrix. Here, X₁ may denote paired MIMO encoder outputs subjected toMIMO encoding.

In the above equation, e^(jφ(q)) may be expressed as follows.

$\begin{matrix}{{{\mathbb{e}}^{j\;{\phi{(q)}}} = {{\cos\;{\phi(q)}} + {j\;\sin\;{\phi(q)}}}},{{\phi(q)} = {\frac{2\;\pi}{N}q}},{q = 0},\ldots\mspace{14mu},{N_{data} - 1},\left( {N = 9} \right)} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 10} \right\rbrack\end{matrix}$

According to another embodiment, the MIMO encoding equation used for thePH-eSM method and the PH-eSM PI method may be expressed as follows.

$\begin{matrix}{{\begin{bmatrix}g_{1,i} \\g_{2,i}\end{bmatrix} = {{{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & 0 \\0 & {\mathbb{e}}^{j\;{\phi{(i)}}}\end{bmatrix}}\begin{bmatrix}1 & {- a} \\a & 1\end{bmatrix}}\begin{bmatrix}e_{1,i} \\e_{2,i}\end{bmatrix}}},{{\phi(i)} = {\frac{2\;\pi}{N}i}},\left( {N = 9} \right),{i = 0},\ldots\mspace{14mu},{\frac{N_{cells}}{2} - 1}} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 11} \right\rbrack\end{matrix}$

The PH-eSM PI method can include two steps. The first step can bemultiplying the rotation matrix with the pair of the input symbols forthe two TX antenna paths, and the second step can be applying complexphase rotation to the symbols for TX antenna 2.

The signals X₁ and X₂ to be transmitted may be generated using twotransmitted symbols (e.g., QAM symbols) S₁ and S₂. In case of atransmission and reception system using OFDM, X₁(f₁), X₂(f₂) may becarried on a frequency carrier f₁ to be transmitted. X₁ may betransmitted via a Tx antenna 1 and X₂ may be transmitted via a Txantenna 2. Accordingly, even when power imbalance is present between twoTx antennas, efficient transmission with minimum loss is possible.

At this time, if the PH-eSM method is applied to symbols mapped to QAM,a value a may be determined according to QAM order as follows. This maybe a value a when the PH-eSM method is applied to symbols mapped touniform QAM.

$\begin{matrix}{{a = {{\frac{\sqrt{2} + 2^{\frac{n}{2}}}{\sqrt{2} + 2^{\frac{n}{2}} - 2}\mspace{14mu}{for}\mspace{14mu} 2^{n}Q\; A\; M} + {2^{n}Q\; A\; M}}},{a = \left\{ \begin{matrix}{\sqrt{2} + 1} & {{{for}\mspace{14mu}{QPSK}} + {QPSK}} \\\frac{\sqrt{2} + 4}{\sqrt{2} + 2} & {{{for}\mspace{14mu} 16\mspace{20mu} Q\; A\; M} + {16\mspace{14mu} Q\; A\; M}} \\\frac{\sqrt{2} + 8}{\sqrt{2} + 6} & {{{for}\mspace{14mu} 64\mspace{14mu} Q\; A\; M} + {64\mspace{14mu} Q\; A\; M}} \\\frac{\sqrt{2} + 16}{\sqrt{2 + 14}} & {{{for}\mspace{14mu} 256\mspace{14mu} Q\; A\; M} + {256\mspace{14mu} Q\; A\; M}}\end{matrix} \right.}} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 12} \right\rbrack\end{matrix}$

At this time, if the PH-eSM PI method is applied to symbols mapped toQAM, a value a may be determined according to QAM order as follows. Thismay be a value a when the PH-eSM PI method is applied to symbols mappedto QAM (uniform QAM).

$\begin{matrix}{{a = {\sqrt{2} + {\left( {2^{\frac{n}{2}} - 1} \right)\mspace{14mu}{for}\mspace{14mu} 2^{n}\mspace{11mu} Q\; A\; M} + {2^{n}\mspace{11mu} Q\; A\; M}}},{a = \left\{ \begin{matrix}{\sqrt{2} + 1} & {{{for}\mspace{14mu}{QPSK}} + {QPSK}} \\{\sqrt{2} + 3} & {{{for}\mspace{14mu} 16\mspace{14mu} Q\; A\; M} + {16\mspace{14mu} Q\; A\; M}} \\{\sqrt{2} + 7} & {{{for}\mspace{14mu} 64\mspace{14mu} Q\; A\; M} + {64\mspace{14mu} Q\; A\; M}} \\{\sqrt{2} + 15} & {{{for}\mspace{14mu} 256\mspace{14mu} Q\; A\; M} + {256\mspace{14mu} Q\; A\; M}}\end{matrix} \right.}} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 13} \right\rbrack\end{matrix}$

At this time, the value a may enable a broadcast/transmission system toobtain good BER performance when considering Euclidean distance andHamming distance if X₁ and X₂ are received through a fully correlatedchannel and are decoded. In addition, the value a may enable thebroadcast/communication system to obtain good BER performance whenconsidering Euclidean distance and Hamming distance if X₁ and X₂ areindependently decoded at the receiver side (that is, if S₁ and S₂ aredecoded using X₁ and S₁ and S₂ are decoded using X₂).

The PH-eSM PI method is different from the PH-eSM method in that thevalue a is optimized in a power imbalanced situation. That is, in thePH-eSM PI method, a rotation angle value is optimized in a powerimbalance situation. In particular, when the PH-ESM PI method is appliedto symbols mapped to non-uniform QAM, the value a may be optimized ascompared to the PH-eSM method.

The above-described value a is merely exemplary and may be changedaccording to embodiment.

The receiver used for the PH-eSM method and the PH-eSM PI method maydecode a signal using the above-described MOMI encoding equation. Atthis time, the receiver may decode a signal using ML, Sub-ML (Sphere)decoding, etc.

Hereinafter, an FRFD PH-eSM PI method will be described. The MIMOencoding equation used for the FRFD PH-eSM PI method is as follows.

$\mspace{610mu}{{\left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 14} \right\rbrack\begin{bmatrix}{X_{1}\left( f_{1} \right)} & {X_{1}\left( f_{2} \right)} \\{X_{2}\left( f_{1} \right)} & {X_{2}\left( f_{2} \right)}\end{bmatrix}} = {\left. \quad{{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & 0 \\0 & {\mathbb{e}}^{j\;{\phi{(q)}}}\end{bmatrix}}\overset{\overset{\mspace{14mu}{{Frequency}\mspace{14mu}{diversity}}}{︷}}{\begin{bmatrix}{S_{1} + {aS}_{2}} & {{a\; S_{3}} - S_{4}} \\{S_{3} + {aS}_{4}} & {{aS}_{1} - S_{2}}\end{bmatrix}}} \right\}\mspace{14mu}{Spatial}\mspace{14mu}{diversity}}}$$\mspace{79mu}{{{or}\mspace{20mu}\begin{bmatrix}{X_{1}\left( f_{1} \right)} & {X_{1}\left( f_{2} \right)} \\{X_{2}\left( f_{1} \right)} & {X_{2}\left( f_{2} \right)}\end{bmatrix}} = {{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & 0 \\0 & {\mathbb{e}}^{j\;{\phi{(q)}}}\end{bmatrix}}\begin{bmatrix}{S_{1} - {aS}_{2}} & {{a\; S_{3}} + S_{4}} \\{S_{3} - {aS}_{4}} & {{aS}_{1} + S_{2}}\end{bmatrix}}}$

By using two antennas X₁ and X₂, it is possible to obtain spatialdiversity. In addition, by utilizing two frequencies f₁ and f₂, it ispossible to obtain frequency diversity.

According to another embodiment of the present invention, a MIMOencoding scheme used for the FRFD PH-eSM PI method may be expressed asfollows.

$\begin{matrix}{\begin{bmatrix}g_{1,{2\; i}} & g_{1,{{2\; i} + 1}} \\g_{2,{2\; i}} & g_{2,{{2\; i} + 1}}\end{bmatrix} = {{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & 0 \\0 & {\mathbb{e}}^{j\;{\phi{(i)}}}\end{bmatrix}}{\quad{\begin{bmatrix}{{\mathbb{e}}_{1,{2\; i}} + {a\; e_{2,{2\; i}}}} & {{a\; e_{1,{{2\; i} + 1}}} - e_{2,{{2\; i} + 1}}} \\{e_{1,{{2\; i} + 1}} + {a\; e_{2,{{2\; i} + 1}}}} & {{a\; e_{1,{2\; i}}} - e_{2,{2\; i}}}\end{bmatrix},\mspace{79mu}{{\phi(i)} = {\frac{2\;\pi}{N}i}},\left( {N = 9} \right),{i = 0},\ldots\mspace{14mu},{\frac{N_{cells}}{4} - 1}}}}} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 15} \right\rbrack\end{matrix}$

The FRFD PH-eSM PI method can take two pairs of NUQ symbols (or UniformQAM symbols or NUC symbols) as input to provide two pairs of MIMO outputsymbols.

The FRFD PH-eSM PI method requires more decoding complexity of areceiver but may have better performance. According to the FRFD PH-eSMPI method, a transmitter generates signals X₁(f₁), X₂(f₁), X₁(f₂) andX₂(f₂) to be transmitted using four transmit symbols S₁, S₂, S₃, S₄. Atthis time, the value a may be equal to the value a used for theabove-described PH-eSM PI method. This may be a value a when the FRFDPH-eSM method is applied to symbols mapped to QAM (uniform QAM).

The MIMO encoding equation of the FRFD PH-eSM PI method may usefrequency carriers f₁ and f₂ unlike the MIMO encoding equation of theabove-described PH-eSM PI method. Therefore, the FRFD PH-eSM PI methodmay efficiently cope not only with power imbalance between Tx antennasbut also with power imbalance between carriers.

In association with MIMO encoding, a structure for additionallyobtaining frequency diversity may include Golden code, etc. The FRFDPH-eSM PI method according to the present invention can obtain frequencydiversity with complexity lower than that of Golden code.

FIG. 28 is a diagram showing a PAM grid of an I or Q side according tonon-uniform QAM according to one embodiment of the present invention.

The above-described PH-eSM PI and FRFD PH-eSM PI methods are applicableto symbols mapped to non-uniform QAM. Non-uniform QAM is a modulationscheme which obtains higher capacity by adjusting a PAM grid value perSNR unlike QAM (uniform QAM). It is possible to obtain more gain byapplying MIMO to symbols mapped to non-uniform QAM. In this case, theencoding equations of the PH-eSM PI and FRFD PH-eSM PI methods are notchanged but a new value “a” may be necessary when the PH-eSM PI and FRFDPH-eSM PI methods are applied to symbols mapped to non-uniform QAM. Thisnew value “a” may be obtained using the following equation.

$\begin{matrix}{{a = {{b\left( {P_{m} - P_{m - 1}} \right)} + {P_{m}\mspace{14mu}{for}\mspace{14mu} 2^{n}Q\; A\; M} + {2^{n}\; Q\; A\; M}}},{m = {2^{\frac{n}{2} - 1}\mspace{14mu}{for}\mspace{14mu} 2^{n}\; Q\; A\; M}}} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 16} \right\rbrack\end{matrix}$

This new value “a” may be a value a when the PH-eSM PI and FRFD PH-eSMPI methods are applied to symbols mapped to non-uniform QAM.

As shown in this figure, the PAM grid of the I or Q side used fornon-uniform QAM is defined and the new value “a” may be obtained using alargest value P_(m) and a second largest value P_(m-1) of this grid. Asignal transmitted via the Tx antenna may be suitably decoded using thisnew value “a” alone.

In the equation for generating the new value “a”, b denotes asub-constellation separation factor. By adjusting the value b, adistance between sub-constellations present in a MIMO encoded signal maybe adjusted. In case of non-uniform AM, since a distance betweenconstellations (or a distance between sub-constellations) is changed, avariable b may be necessary. Examples of the value b may include√{square root over (2)}/2. This value may be obtained by Hammingdistance and Euclidean distance based on a point having highest power ona constellation and points adjacent thereto.

In case of non-uniform QAM, since a grid value optimized per SNR (orcode-rate of FEC) is used, the sub-constellation separation factor “b”may also use a value optimized per SNR (or code-rate of FEC). That is,capacity of constellation transmitted after MIMO encoding may beanalyzed according to the value “b” and the SNR (or code-rate of FEC) tofind the value “B” for providing maximum capacity at a specific SNR(target SNR).

For example, if NU-16 QAM+NU-16 QAM MIMO and P={1, 3.7}, the new value“a” may be computed by a=√{square root over (2)}/2(3.7−1)+3.7. At thistime, the value b is set to √{square root over (2)}/2.

For example, NU-64 QAM+NU-64 QAM MIMO and P={1, 3.27, 5.93, 10.27}, thenew value “a” may be computed by a=√{square root over(2)}/2(10.27−5.93)+10.27. At this time, the value b is set to √{squareroot over (2)}/2.

For example, if NU-256 QAM+NU-256 QAM MIMO and P={1, 1.02528, 3.01031,3.2249, 5.2505, 6.05413, 8.48014, 11.385}, the new value “a” may becomputed by a=√{square root over (2)}/2(11.385−8.48014)+11.385. At thistime, the value b is set to √{square root over (2)}/2.

As described above, the PH-eSM PI and FRFD PH-eSM PI methods may beapplied to symbols mapped to non-uniform QAM. Similarly, the PH-eSMmethod may also be applied to symbols mapped to non-uniform QAM. In thiscase, the value “a” may be determined according to the PH-eSM method. Anequation for determining the value “a” is as follows.

$\begin{matrix}{{a = \frac{{b\left( {P_{m} - P_{m - 1}} \right)} + P_{m} + 1}{{b\left( {P_{m} - P_{m - 1}} \right)} + P_{m} - 1}}{{{{for}\mspace{14mu} 2^{n}\; Q\; A\; M} + {2^{n}\; Q\; A\; M}},{m = {2^{\frac{n}{2} - 1}\mspace{14mu}{for}\mspace{14mu} 2^{n}\; Q\; A\; M}}}} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 17} \right\rbrack\end{matrix}$

This new value “a” may be a value a when the PH-eSM method is applied tosymbols mapped to non-uniform QAM.

b is a sub-constellation separation factor as described above. Asdescribed above, the value “b” may be optimized to suit each SNR (orcode-rate of FEC) by analyzing capacity of the encoded constellation.

For example, if NU-16 QAM+NU-16 QAM MIMO and P={1, 3.7}, the new value“a” may be computed by a=√{square root over (2)}/2(3.7−1)+3.7+1/√{squareroot over (2)}/2(3.7−1)+3.7−1. At this time, the value b is set to√{square root over (2)}/2.

For example, if NU-64 QAM+NU-64 QAM MIMO and P={1, 3.27, 5.93, 10.27},the new value “a” may be computed by a=√{square root over(2)}/2(10.27−5.93)+10.27+1/√{square root over(2)}/2(10.27−5.93)+10.27−1. At this time, the value b is set to √{squareroot over (2)}/2.

For example, if NU-256 QAM+NU-256 QAM MIMO and P={1, 1.02528, 3.01031,3.2249, 5.2505, 6.05413, 8.48014, 11.385}, the new value “a” may becomputed by a=√{square root over(2)}/2(11.385−8.48014)+11.385+1/√{square root over(2)}/2(11.385−8.48014)+11.385−1. At this time, the value b is set to√{square root over (2)}/2.

Hereinafter, a method of determining NU-QAN and MIMO encoding parameter“a” in the MIMO encoding method (the PH-eSM PI method and the FRFDPH-eSM PI method) applied to symbols mapped to NU-QAM optimized per SNR(or code-rate of FEC) will be described.

In order to apply the PH-eSM PI method and the FRFD PH-eSM PI method tosymbols mapped to NU-QAM per SNR (or code-rate of FEC), the followingtwo elements should be considered. First, in order to obtain shapinggain, NU-QAM optimized per SNR should be found. Second, the MIMOencoding parameter “a” should be determined in each NU-QAM optimized perSNR.

The MIMO encoding scheme (the PH-eSM PI method and the FRFD PH-eSM PImethod), NU-QAM and MIMO encoding parameter suitable for each SNR may bedetermined through capacity analysis as follows. Here, capacity may meanBICM capacity. The process of determining a NU-QAM and MIMO encodingparameter suitable for each SNR may be performed in consideration ofcorrelated channel and power imbalanced channel.

If computation for capacity analysis at MIMO channel is acceptable, itis possible to determine NU-QAM for optimized MIMO, which providesmaximum capacity at a target SNR.

If computation is not acceptable, NU-QAM for MIMO may be determinedusing NU-QAM optimized for SISO. First, with respect to NU-QAM optimizedfor SISO per SNR (or code-rate of FEC), BER performance comparison maybe performed in a non-power imbalanced MIMO channel environment. ThroughBER performance comparison, NU-QAM for MIMO may be determined fromNU-QAM (FEC code rate 5/15, 6/15, . . . 13/15) optimized for SISO. Forexample, constellation for MIMO at code-rate 5/15 of 12 bpcu(NU-64QAM+NU-64QAM) may be set to NU-64QAM corresponding to SISOcode-rate 5/15. In addition, for example, constellation of MIMO FEC coderate 6/15 may be constellation of SISO FEC code rate 5/15. That is,constellation of SISO FEC code rate 5/15 may suitable for MIMO FEC coderate 6/15.

Once NU-QAM is determined, the MIMO encoding parameter “a” optimized perSNR may be determined at a power imbalanced MIMO channel throughcapacity analysis based on the determined NU-QAM. For example, in the 12bpcu and 5/15 code rate environment, the value a may be 0.1571.

Hereinafter, measurement for performance of MIMO encoding according tothe value a will be described. For performance measurement, BICMcapacity may be measured. Through this operation, the value a capable ofmaximizing BICM capacity is determined.

BICM capacity may be expressed by the following equations.

$\begin{matrix}{\mspace{590mu}\left\lbrack {{Math}\mspace{14mu}{figure}\mspace{11mu} 18} \right\rbrack} & \; \\{{{BICMcap} = {\int_{\varphi}^{\;}{\left( {\sum\limits_{i}{\begin{pmatrix}{{\int_{Y}{{p\left( {{b_{i} = 0},Y} \right)}\log_{2}\frac{p\left( {{b_{i} = 0},Y} \right)}{{p\left( {b_{i} = 0} \right)}{p(Y)}}{\mathbb{d}Y}}} +} \\{\int_{Y}{{p\left( {{b_{i} = 1},Y} \right)}\log_{2}\frac{p\left( {{b_{i} = 1},Y} \right)}{{p\left( {b_{i} = 1} \right)}{p(Y)}}{\mathbb{d}Y}}}\end{pmatrix}{p(\varphi)}}} \right){\mathbb{d}\varphi}}}}\begin{matrix}{{p\left( {{b_{i} = j},Y} \right)} = {{p\left( {{Y❘b_{i}} = j} \right)} \cdot {{p\left( {b_{i} = j} \right)}\mspace{194mu}\left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 19} \right\rbrack}}} \\{= {\sum\limits_{M_{i}}{{p\left( {{Y❘S} = M_{j}} \right)} \cdot \frac{1}{M^{2}}}}} \\{= {\sum\limits_{M_{i}}{\frac{1}{\pi\;\sigma^{2}}{{\mathbb{e}}^{\frac{- {{Y - {H_{PI}{PM}_{j}}}}^{2}}{\sigma^{2}}} \cdot \frac{1}{M^{2}}}}}}\end{matrix}} & \; \\\begin{matrix}{\frac{p\left( {{b_{i} = j},Y} \right)}{{p\left( {b_{i} = j} \right)}{p(Y)}} = {\frac{p\left( {{Y❘b_{i}} = j} \right)}{p(Y)}\mspace{275mu}\left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 20} \right\rbrack}} \\{= \frac{p\left( {{Y❘b_{i}} = j} \right)}{\sum\limits_{j}{p\left( {{b_{i} = j},Y} \right)}}} \\{= \frac{\sum\limits_{M_{i}}{\frac{1}{\pi\;\sigma^{2}}{{\mathbb{e}}^{\frac{- {{Y - {{II}_{PI}{PM}_{j}}}}^{2}}{\sigma^{2}}} \cdot \frac{2}{M^{2}}}}}{\sum\limits_{j}{\sum\limits_{M_{i}}{\frac{1}{\pi\;\sigma^{2}}{{\mathbb{e}}^{\underset{\sigma^{2}}{- {{Y - {H_{PI}{PM}_{j}}}}^{2}}} \cdot \frac{1}{M^{2}}}}}}}\end{matrix} & \;\end{matrix}$

Here, p(b_(i)=0)=p(b_(i)=1)=0.5. In addition, p(S=Mj)=1/M², p(φ)=1/π.Here, Sε{constellation set} and M may mean a constellation size.

Here, Y may be expressed as follows.

$\begin{matrix}{{\begin{bmatrix}{Y_{1}\left( f_{1} \right)} \\{Y_{2}\left( f_{1} \right)}\end{bmatrix} = {{{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & {\alpha \cdot {\mathbb{e}}^{j\;\varphi}} \\{\mathbb{e}}^{j\;\varphi} & \alpha\end{bmatrix}}\begin{bmatrix}{X_{1}\left( f_{1} \right)} \\{X_{2}\left( f_{1} \right)}\end{bmatrix}} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}}}\mspace{79mu}{Y = \begin{bmatrix}{Y_{1}\left( f_{1} \right)} \\{Y_{2}\left( f_{1} \right)}\end{bmatrix}}\mspace{79mu}{H_{PI} = {\frac{1}{\sqrt{1 + \alpha^{2}}}\begin{bmatrix}1 & {\alpha \cdot {\mathbb{e}}^{j\;\varphi}} \\{\mathbb{e}}^{j\;\varphi} & \alpha\end{bmatrix}}}\mspace{79mu}{X = \begin{bmatrix}{X_{1}\left( f_{1} \right)} \\{X_{2}\left( f_{1} \right)}\end{bmatrix}}\mspace{79mu}{n = \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}}} & \left\lbrack {{Math}\mspace{14mu}{figure}\mspace{14mu} 21} \right\rbrack\end{matrix}$

That is, Y=H_(PI)X+n. Here, n may be AWGN. X may be expressed by X=PS asdescribed above. BICM capacity may assume AWGN and individuallyidentically distributed (IID) input. In addition, (I) may mean a uniformrandom variable U(0, π). In order to consider a correlated channelenvironment and a power imbalanced channel environment which may occurupon using MIMO, H_(PI) of the above-described equation may be assumed.At this time, an alpha value is a power imbalance (PI) factor and may bePI 9 dB: 0.354817, PI 6 dB: 0.501187 or PI 3 dB: 0.70711 according toPI. Here, Mjε{constellation set|bi=j}.

Through this equation, BICM capacity according to the value a may bemeasured to determine an optimal value a.

That is, the method for determining the MIMO encoding parameter mayinclude two steps as follows.

Step 1. Through BER performance comparison for constellation of SISO FECcode rate, NU-QAM having optimal performance of MIMO FEC code-rate to befound is selected.

Step 2. Based on NU-QAM obtained in Step 1, an encoding parameter “a”having optimal performance may be determined through the above-describedBICM capacity analysis.

The value a according to constellation per code rate is shown in thefollowing table. This is merely an example of the value a according tothe present invention.

TABLE 34 8 bpcu 12 bpcu Code rate Constellation a Constellation a 5/15QAM-16 0 NUQ-64 for CR = 5/15  0.1571 6/15 QAM-16 0.0035 NUQ-64 for CR =5/15  0.1396 7/15 QAM-16 0.1222 NUQ-64 for CR = 6/15  0.2129 8/15 QAM-160.1671 NUQ-64 for CR = 8/15  0.2548 9/15 QAM-16 0.1710 NUQ-64 for CR =11/15 0.2653 10/15  QAM-16 0.1780 NUQ-64 for CR = 12/15 0.2566 11/15 QAM-16 0.1798 NUQ-64 for CR = 12/15 0.2548 12/15  QAM-16 0.1815 NUQ-64for CR = 13/15 0.2563 13/15  QAM-16 0.1815 NUQ-64 for CR = 13/15 0.2583

The PH-eSM PI method can be applied for 8 bpcu and 12 bpcu with 16K and64K FECBLOCK. PH-eSM PI method can use the MIMO encoding parametersdefined in the above table for each combination of a value of bits perchannel use and code rate of an FECBLOCK. Detailed constellationscorresponding to the illustrated MIMO parameter table are describedbelow.

The above table shows constellation and MIMO encoding parameter aoptimized per code rate. For example, in case of 12 bpcu and code rateof 6/15 of MIMO encoding, constellation of NUQ-64 which is used in caseof code rate of 5/15 of SISO encoding may be used. That is, in case of12 bpcu and code rate of 6/15 of MIMO encoding, constellation of coderate of 5/15 of SISO encoding may be an optimal value. At this time, thevalue “a” may be 0.1396.

TABLE 35 10 bpcu Code rate Constellation a 5/15 QAM-16/NUQ-64 for CR =5/15  0 6/15 QAM-16/NUQ-64 for CR = 5/15  0 7/15 QAM-16/NUQ-64 for CR =6/15  0 8/15 QAM-16/NUQ-64 for CR = 8/15  0 9/15 QAM-16/NUQ-64 for CR =11/15 0 10/15  QAM-16/NUQ-64 for CR = 12/15 0 11/15  QAM-16/NUQ-64 forCR = 12/15 0 12/15  QAM-16/NUQ-64 for CR = 13/15 0 13/15  QAM-16/NUQ-64for CR = 13/15 0

For the 10 bpcu MIMO case, PH-eSM PI method can use the MIMO encodingparameters defined in the above table. These parameters are especiallyuseful when there is a power imbalance between horizontal and verticaltransmission (e.g. 6 dB in current U.S. Elliptical pole network). TheQAM-16 can be used for the TX antenna of which the transmission power isdeliberately attenuated. Detailed constellations corresponding to theillustrated MIMO parameter table are described below.

The FRFD PH-eSM PI method can use the MIMO encoding parameters of thePH-eSM PI method defined in the above tables for each combination of avalue of bit per channel use and code rate of an FECBLOCK.

The values “a” of the above table may be determined in consideration ofEuclidean distance and Hamming distance and are optimal in code rate andconstellation. Accordingly, it is possible to obtain excellent BERperformance.

FIG. 29 is a diagram showing MIMO encoding input/output when the PH-eSMPI method is applied to symbols mapped to non-uniform 64 QAM accordingto one embodiment of the present invention.

Even when the FRFD PH-eSM PI according to one embodiment of the presentinvention is applied to symbols mapped to non-uniform QAM, aninput/output diagram similar to this figure may be obtained. If theabove-described new value “a” and the encoding matrix of the MIMOencoding equation are used, the constellation shown in this figure maybe obtained by the MIMO encoder input and output.

In the MIMO encoder output of this figure, sub-constellations may belocated. At this time, a distance between sub-constellations may bedetermined by the above-described sub-constellation separation factor“b”. The MIMO encoded constellations may maintain a non-uniformproperty.

FIG. 30 is a graph for comparison in performance of MIMO encodingschemes according to the embodiment of the present invention.

This graph shows comparison in capacity between MIMO encoding schemes inan 8-bpcu/outdoor environment. The PH-eSM PI and FRFD PH-eSM PI methodsof the present invention exhibit better performance than an existingMIMO encoding scheme (GC, etc.) in terms of capacity. This means thatmore efficient transmission is possible in the same environment ascompared with other MIMO techniques.

FIG. 31 is a graph for comparison in performance of MIMO encodingschemes according to the embodiment of the present invention.

This graph shows comparison in capacity according to MIMO encodingschemes in an 8-bpcu/outdoor/HPI9 environment. The PH-eSM PI and FRFDPH-eSM PI methods of the present invention exhibits better performancethan an existing MIMO encoding scheme (SM, GC, PH-eSM, etc.) in terms ofcapacity. This means that more efficient transmission is possible in thesame environment as compared with other MIMO techniques.

FIG. 32 is a graph for comparison in performance of MIMO encodingschemes according to the embodiment of the present invention.

This graph shows comparison in BER according to MIMO encoding schemes inan 8-bpcu/outdoor/random BI, TI environment. The PH-eSM PI and FRFDPH-eSM PI methods of the present invention exhibits better performancethan an existing MIMO encoding scheme (GC, etc.) in terms of BER. Thismeans that more efficient transmission is possible in the sameenvironment as compared with other MIMO techniques.

FIG. 33 is a graph for comparison in performance of MIMO encodingschemes according to the embodiment of the present invention.

This graph shows comparison in BER according to MIMO encoding schemes inan 8-bpcu/outdoor/HPI9/random BI, TI environment. BER Performance of thePH-eSM PI and FRFD PH-eSM PI methods of the present invention is betterthan that of existing MIMO encoding (SM, GC, PH-eSM, etc.) in terms ofcapacity. This means that more efficient transmission is possible in thesame environment as compared other MIMO techniques.

FIG. 34 is a diagram showing an embodiment of QAM-16 according to thepresent invention.

This figure shows a constellation shape of QAM-16 on a complex plane.This figure shows the constellation shape of QAM-16 for all code rates.

FIG. 35 is a diagram showing an embodiment of NUQ-64 for 5/15 code rateaccording to the present invention.

This figure shows the constellation shape of QAM-64 for 5/15 code rateon a complex plane.

FIG. 36 is a diagram showing an embodiment of NUQ-64 for 6/15 code rateaccording to the present invention.

This figure shows the constellation shape of QAM-64 for 6/15 code rateon a complex plane.

FIG. 37 is a diagram showing an embodiment of NUQ-64 for 7/15 code rateaccording to the present invention.

This figure shows the constellation shape of QAM-64 for 7/15 code rateon a complex plane.

FIG. 38 is a diagram showing an embodiment of NUQ-64 for 8/15 code rateaccording to the present invention.

This figure shows the constellation shape of QAM-64 for 8/15 code rateon a complex plane.

FIG. 39 is a diagram showing an embodiment of NUQ-64 for 9/15 and 10/15code rates according to the present invention.

This figure shows the constellation shape of QAM-64 for 9/15 and 10/15code rates on a complex plane.

FIG. 40 is a diagram showing an embodiment of NUQ-64 for 11/15 code rateaccording to the present invention.

This figure shows the constellation shape of QAM-64 for 11/15 code rateon a complex plane.

FIG. 41 is a diagram showing an embodiment of NUQ-64 for 12/15 code rateaccording to the present invention.

This figure shows the constellation shape of QAM-64 for 12/15 code rateon a complex plane.

FIG. 42 is a diagram showing an embodiment of NUQ-64 for 13/15 code rateaccording to the present invention.

This figure shows the constellation shape of QAM-64 for 13/15 code rateon a complex plane.

FIG. 43 is a method of transmitting broadcast signals according to anembodiment of the present invention.

The method includes formatting input streams, LDPC encoding, bitinterleaving, mapping onto a constellations, MIMO encoding, building asignal frame and/or modulating and transmitting.

In step of formatting input streams, the above-described inputformatting module may format input streams into DP data. DP data canmeans Data Pipe.

In step of LDPC encoding, the above-described BICM module may LDPCencode the DP data according to a code rate. The code rate can beconfigurable. By adjusting the code rate, LDPC encoding can be changed.The LDPC encoding may correspond to above-described LDPC encoding.

In step of bit interleaving, the above-described BICM module may conductbit interleaving. The bit interleaving may correspond to above-describedbit interleaving.

In step of mapping onto a constellations, the above-described BICMmodule may map the bit interleaved DP data onto constellations accordingto one of QAM (Quadrature Amplitude Modulation), NUQ (Non-Uniform QAM)or NUC(Non-Uniform Constellation). The QAM, NUQ, NUC may correspond toabove-described QAM, NUQ, NUC. The constellations may also be referredas a constellation set. The data in each DP path can be mapped ontodifferent constellations. For example, DP data in a DP path can bemapped onto QAM, while DP data in other DP path can be mapped onto NUQ.

In step of MIMO encoding, the above-described BICM module may MIMOencode the mapped DP data by using a MIMO encoding matrix having a MIMOencoding parameter. The MIMO encoding may correspond to above-describedMIMO encoding. The MIMO encoding can be performed on data which ismapped onto NUQ or NUC.

In step of building a signal frame, the above-described frame buildingmodule may build at least one signal frame by mapping the MIMO encodedDP data. The frame building may correspond to above-described framebuilding.

In step of modulating and transmitting, the above-described OFDMmodulating module may modulate data in the built signal frame byOrthogonal Frequency Division Multiplexing, OFDM, method. Also, the OFDMmodulating module may transmit the broadcast signals having themodulated data. The modulating and transmitting may correspond toabove-described modulating and transmitting.

In a method of transmitting broadcast signal according to otherembodiment of the present invention, the MIMO encoding can be performedaccording to either FR-SM (Full-rate spatial multiplexing) method orFRFD-SM (Full-rate Full-diversity spatial multiplexing) method. TheFR-SM method and FRFD-SM method may correspond to above-described MIMOencoding method, FR-SM and FRFD-SM, which also can be referred as PH-eSMPI and FRFD PH-eSM PI method.

In a method of transmitting broadcast signal according to anotherembodiment of the present invention, the QAM, the NUQ and the NUC can bedefined depending on the code rate.

In a method of transmitting broadcast signal according to anotherembodiment of the present invention, the MIMO encoding parameter can bedefined based on one of the QAM, the NUQ or the NUC. The MIMO encodingparameter may correspond to above-described ‘a’. The MIMO encodingparameter can be determined constellations (QAM, NUQ or NUC) and/or acode rate, as described above.

The above-described steps can be omitted or replaced by steps executingsimilar or identical functions according to design.

FIG. 44 is a method of receiving broadcast signals according to anembodiment of the present invention.

The method includes receiving and de-modulating, parsing a signal frame,MIMO decoding, de-mapping from constellations, bit de-interleaving, LDPCdecoding and/or de-formatting.

In step of receiving and de-modulating, the above-described OFDMdemodulating module may receive the broadcast signals having at leastone signal frame and demodulate data in the at least one signal frame byan Orthogonal Frequency Division Multiplexing, OFDM, method. Thereceiving and de-modulating may correspond to above-described receivingand de-modulating.

In step of parsing a signal frame, the above-described frame parsingmodule may parse the at least one signal frame by de-mapping Data Pipe,DP, data. The parsing a signal frame may correspond to parsing a signalframe.

In step of MIMO decoding, the above-described BICM module may MIMOdecode the DP data by using a MIMO decoding matrix having a MIMOdecoding parameter. The MIMO decoding matrix may correspond to aninverse matrix of the above-described MIMO encoding matrix. The MIMOdecoding parameter may correspond to above-described MIMO encodingparameter ‘a’. The MIMO decoding matrix can have parameter ‘a’, sincethe MIMO decoding matrix can be an inverse matrix of MIMO encodingmatrix.

In step of de-mapping from constellations, the above-described BICMmodule may de-map the MIMO decoded DP data from constellations accordingto one of QAM (Quadrature Amplitude Modulation), NUQ (Non-Uniform QAM)or NUC(Non-Uniform Constellation). The QAM, NUQ, NUC may correspond toabove-described QAM, NUQ, NUC. The constellations may also be referredas a constellation set. The data in each DP path can be de-mapped fromdifferent constellations. For example, DP data in a DP path can bedemapped from QAM, while DP data in other DP path can be demapped fromNUQ.

In step of bit de-interleaving, the above-described BICM module may bitde-interleave the de-mapped DP data. The bit de-interleaving maycorrespond to above-described bit de-interleaving.

In step of LDPC decoding, the above-described BICM module may LDPCdecode the bit de-interleaved DP data according to a code rate. The LDPCdecoding can be an inverse process of above-described LDPC encoding. TheLDPC decoding may correspond to above-described LDPC decoding.

In step of de-formatting, the above-described output processor mayoutput process (de-format) the LDPC decoded DP data into output streams.The deformatting may correspond to above-described output processing.

In a method of receiving broadcast signal according to other embodimentof the present invention, the MIMO decoding is performed according toeither FR-SM (Full-rate spatial multiplexing) method or FRFD-SM(Full-rate Full-diversity spatial multiplexing) method. The FR-SM methodand FRFD-SM method may correspond to above-described MIMO encodingmethod, FR-SM and FRFD-SM, which also can be referred as PH-eSM PI andFRFD PH-eSM PI method.

In a method of receiving broadcast signal according to anotherembodiment of the present invention, the QAM, the NUQ and the NUC can bedefined depending on the code rate.

In a method of receiving broadcast signal according to anotherembodiment of the present invention, the MIMO decoding parameter can bedefined based on one of the QAM, the NUQ or the NUC. The MIMO decodingparameter may correspond to above-described ‘a’. The MIMO decodingparameter can be determined constellations (QAM, NUQ or NUC) and/or acode rate, as described above.

The above-described steps can be omitted or replaced by steps executingsimilar or identical functions according to design.

Although the description of the present invention is explained withreference to each of the accompanying drawings for clarity, it ispossible to design new embodiment(s) by merging the embodiments shown inthe accompanying drawings with each other. And, if a recording mediumreadable by a computer, in which programs for executing the embodimentsmentioned in the foregoing description are recorded, is designed innecessity of those skilled in the art, it may belong to the scope of theappended claims and their equivalents.

An apparatus and method according to the present invention may benon-limited by the configurations and methods of the embodimentsmentioned in the foregoing description. And, the embodiments mentionedin the foregoing description can be configured in a manner of beingselectively combined with one another entirely or in part to enablevarious modifications.

In addition, a method according to the present invention can beimplemented with processor-readable codes in a processor-readablerecording medium provided to a network device. The processor-readablemedium may include all kinds of recording devices capable of storingdata readable by a processor. The processor-readable medium may includeone of ROM, RAM, CD-ROM, magnetic tapes, floppy discs, optical datastorage devices, and the like for example and also include such acarrier-wave type implementation as a transmission via Internet.Furthermore, as the processor-readable recording medium is distributedto a computer system connected via network, processor-readable codes canbe saved and executed according to a distributive system.

It will be appreciated by those skilled in the art that variousmodifications and variations can be made in the present inventionwithout departing from the spirit or scope of the inventions. Thus, itis intended that the present invention covers the modifications andvariations of this invention provided they come within the scope of theappended claims and their equivalents.

Both apparatus and method inventions are mentioned in this specificationand descriptions of both of the apparatus and method inventions may becomplementarily applicable to each other.

Various embodiments have been described in the best mode for carryingout the invention.

The present invention is available in a series of broadcast signalprovision fields.

It will be apparent to those skilled in the art that variousmodifications and variations can be made in the present inventionwithout departing from the spirit or scope of the inventions. Thus, itis intended that the present invention covers the modifications andvariations of this invention provided they come within the scope of theappended claims and their equivalents.

The invention claimed is:
 1. A method of transmitting broadcast signals,the method comprising: encoding PLP (Physical Layer Pipe) data accordingto a code rate; bit interleaving the encoded PLP data; demultiplexingthe bit interleaved PLP data into first data cells and second datacells; mapping the first data cells onto first symbols in a first NUC(Non-Uniform Constellation), and mapping the second data cells ontosecond symbols in a second NUC; MIMO (Multi-Input Multi-Output) encodingpairs of the first and second symbols, wherein the MIMO encoding furtherincludes: applying a rotation matrix rotating the pairs based on a MIMOparameter, wherein value of the MIMO parameter is defined based on thecode rate and types of the first and second NUCs, and applying a phaserotation to the second symbols in the pairs; time interleaving the MIMOencoded data; building at least one signal frame by mapping the timeinterleaved data; and modulating data in the built signal frame by OFDM(Orthogonal Frequency Division Multiplexing) method and transmitting thebroadcast signals having the modulated data.
 2. The method of claim 1,wherein the signal frame includes signaling data for signaling the PLPdata, wherein the signaling data includes information for indicating thetypes of the first and second NUCs.
 3. The method of claim 2, whereinthe signaling data further includes information for indicating whichprocesses are used for the MIMO encoding.
 4. The method of claim 2,wherein the signaling data further includes information for indicatingthe code rate for the PLP data.
 5. An apparatus for transmittingbroadcast signals, the apparatus comprising: an encoder that encodes PLP(Physical Layer Pipe) data according to a code rate; a bit interleaverthat bit interleaves the encoded PLP data; a demux that demultiplexesthe bit interleaved PLP data into first data cells and second datacells; a mapper that maps the first data cells onto first symbols in afirst NUC (Non-Uniform Constellation), and maps the second data cellsonto second symbols in a second NUC; a MIMO (Multi-Input Multi-Output)encoder that MIMO encodes pairs of the first and second symbols, whereinthe MIMO encoder applies a rotation matrix rotating the pairs based on aMIMO parameter, wherein value of the MIMO parameter is defined based onthe code rate and types of the first and second NUCs, wherein the MIMOencoder further applies a phase rotation to the second symbols in thepairs; a time interleaver that time interleaves the MIMO encoded data; aframe builder that builds at least one signal frame by mapping the timeinterleaved data; and a modulating module that modulates data in thebuilt signal frame by OFDM (Orthogonal Frequency Division Multiplexing)method and transmits the broadcast signals having the modulated data. 6.The apparatus of claim 5, wherein the signal frame includes signalingdata for signaling the PLP data, wherein the signaling data includesinformation for indicating the types of the first and second NUCs. 7.The apparatus of claim 6, wherein the signaling data further includesinformation for indicating which processes are used for the MIMOencoding.
 8. The apparatus of claim 6, wherein the signaling datafurther includes information for indicating the code rate for the PLPdata.